Power conversion system and magnetic component thereof

ABSTRACT

A power conversion system and a magnetic component thereof are provided. The magnetic component includes a magnetic core assembly, two windings and an air gap. The magnetic core assembly includes two substrates, four winding pillars and an auxiliary pillar unit. The four winding pillars and the auxiliary pillar unit are located between the two substrates. A connecting line of centers of the winding pillars forms a quadrangle which has a first diagonal line and a second diagonal line. One winding is wound around two winding pillars on the first diagonal line, and magnetic fluxes on these two winding pillars have the same direction and amount. The other winding is wound around the other two winding pillars located on the second diagonal line, and magnetic fluxes on these two winding pillars have the same direction and amount. The directions of the magnetic fluxes on the two neighboring winding pillars are opposite.

CROSS-REFERENCE TO RELATED APPLICATION

This application claims priority to China Patent Application No.201910883647.6 filed on Sep. 18, 2019 and claims priority to ChinaPatent Application No. 202010774103.9 filed on Aug. 4, 2020. The entirecontents of the above-mentioned patent applications are incorporatedherein by reference for all purposes.

FIELD OF THE INVENTION

The present disclosure relates to a power conversion system and amagnetic component thereof, and more particularly to a power conversionsystem and a magnetic component thereof having a magnetic core assemblycapable of dividing and sharing the AC magnetic flux flowing through thewinding pillar.

BACKGROUND OF THE INVENTION

In conventional applications of non-isolated step-down DC-DC converterswith high output current, a two-phase buck circuit with parallelconfiguration is employed. As shown in FIG. 1, the parallelconfiguration is utilized to reduce the current stress on switches, andthe switches in every phase of the buck circuit are driven by twosignals having 180 degrees out of phase with respect to each other, soas to reduce the current ripple. However, in the buck circuit, theswitching duty ratio equals the voltage transmission ratio of the outputvoltage to the input voltage, i.e., Vo=Vin*D. Accordingly, in theapplications that the input voltage is larger than the output voltage,the switching duty ratio is reduced, which causes the buck circuitunable to operate with the best performance.

Therefore, there is a need of providing a power conversion system and amagnetic component thereof to obviate the drawbacks encountered from theprior arts.

SUMMARY OF THE INVENTION

It is an objective of the present disclosure to provide a powerconversion system and a magnetic component thereof. The power conversioncircuit of the power conversion system is a multi-phase buck converterwith extended duty ratio. Compared with the conventional buck circuitunder the same input and output conditions, the power conversion circuitof the present disclosure can increase the duty ratio and reduce theamount of voltage jump while turning on or off switches. Therefore, theswitching loss is reduced, and the efficiency is improved. In addition,through the special structure of the magnetic core assembly of the powerconversion system, the AC magnetic flux flowing through the windingpillar is shared. Accordingly, the thickness of the substrate of themagnetic core assembly is reduced, and the height of the powerconversion system product is reduced, which makes the power conversionsystem product become thinner and increases the applicability. Further,in the power conversion system, the power density is improved, and thevertical thermal resistance is reduced.

In accordance with an aspect of the present disclosure, there isprovided a magnetic component. The magnetic component includes amagnetic core assembly, two windings and an air gap. The magnetic coreassembly includes two substrates, four winding pillars and an auxiliarypillar unit. The four winding pillars and the auxiliary pillar unit aredisposed on at least one of the two substrates and are located betweenthe two substrates. A connecting line of centers of the four windingpillars forms a quadrangle, and the quadrangle has a first diagonal lineand a second diagonal line. The auxiliary pillar unit is located amongthe four winding pillars. One of the two windings is wound around two ofthe four winding pillars which are located on the first diagonal line,and magnetic fluxes on the two winding pillars on the first diagonalline have the same direction and amount. The other winding is woundaround the other two winding pillars located on the second diagonalline, and magnetic fluxes on the two winding pillars on the seconddiagonal line have the same direction and amount. The directions of themagnetic fluxes on the two neighboring winding pillars are opposite. Themagnetic flux flowing out of any of the four windings flows to the twoneighboring winding pillars and the auxiliary pillar unit to form threeclosed magnetic flux loops. The air gap is disposed on the auxiliarypillar unit.

In accordance with another aspect of the present disclosure, there isprovided a power conversion system. The power conversion system includesa power conversion circuit and a magnetic component. The powerconversion circuit includes an input port, an output port, a firstswitching power conversion unit, a second switching power conversionunit and a storage device. The input port is configured to receive aninput voltage. The output port is configured to output an outputvoltage. The first switching power conversion unit and the secondswitching power conversion unit are connected in series. Each of thefirst and second switching power conversion units includes a firstswitch, a second switch and an inductor. In each of the first and secondswitching power conversion units, one terminal of the first switch iselectrically connected to one terminal of the second switch and oneterminal of the inductor, the other terminal of the second switch isgrounded, and the other terminal of the inductor is electricallyconnected to the output port. The other terminal of the first switch ofthe first switching power conversion unit is electrically connected tothe input port, and the other terminal of the first switch of the secondswitching power conversion unit is electrically connected to the firstswitch of the first switching power conversion unit. The storage deviceis electrically connected between the first switch and the inductor ofthe first switching power conversion unit. The magnetic componentincludes a magnetic core assembly, two windings and an air gap. Themagnetic core assembly includes two substrates, four winding pillars andan auxiliary pillar unit. The four winding pillars and the auxiliarypillar unit are disposed on at least one of the two substrates and arelocated between the two substrates. A connecting line of centers of thefour winding pillars forms a quadrangle, and the quadrangle has a firstdiagonal line and a second diagonal line. The auxiliary pillar unit islocated among the four winding pillars. One of the two windings is woundaround two of the four winding pillars which are located on the firstdiagonal line, and magnetic fluxes on the two winding pillars on thefirst diagonal line have the same direction and amount. The otherwinding is wound around the other two winding pillars located on thesecond diagonal line, and magnetic fluxes on the two winding pillars onthe second diagonal line have the same direction and amount. Thedirections of the magnetic fluxes on the two neighboring winding pillarsare opposite. The magnetic flux flowing out of any of the four windingsflows to the two neighboring winding pillars and the auxiliary pillarunit to form three closed magnetic flux loops. The air gap is disposedon the auxiliary pillar unit. Two windings of the two inductors of thefirst and second switching power conversion units are the two windingsof the magnetic component wound around the magnetic core assembly.

In accordance with another aspect of the present disclosure, there isprovided a power conversion system. The power conversion system includesa power conversion circuit and a magnetic component. The powerconversion circuit includes an input port, an output port, a firstswitching power conversion unit, a second switching power conversionunit and two storage devices. The input port is configured to receive aninput voltage. The output port is configured to output an outputvoltage. The first switching power conversion unit and the secondswitching power conversion unit are connected in series. Each of thefirst and second switching power conversion units includes a firstswitch, a second switch, a third switch and an inductor. In each of thefirst and second switching power conversion units, a first terminal ofthe first switch is electrically connected to the input port, and asecond terminal of the first switch is electrically connected to oneterminal of the second switch, the third switch and one terminal of theinductor. The other terminal of the second switch is electricallyconnected to the second terminal of the first switch of the otherswitching power conversion unit, and the other terminal of the inductoris electrically connected to the output port. One of the two storagedevices is electrically connected between the first switch and theinductor of the first switching power conversion unit, and the otherstorage device is electrically connected between the first switch andthe inductor of the second switching power conversion unit. The magneticcomponent includes a magnetic core assembly, two windings and an airgap. The magnetic core assembly includes two substrates, four windingpillars and an auxiliary pillar unit. The four winding pillars and theauxiliary pillar unit are disposed on at least one of the two substratesand are located between the two substrates. A connecting line of centersof the four winding pillars forms a quadrangle, and the quadrangle has afirst diagonal line and a second diagonal line. The auxiliary pillarunit is located among the four winding pillars. One of the two windingsis wound around two of the four winding pillars which are located on thefirst diagonal line, and magnetic fluxes on the two winding pillars onthe first diagonal line have the same direction and amount. The otherwinding is wound around the other two winding pillars located on thesecond diagonal line, and magnetic fluxes on the two winding pillars onthe second diagonal line have the same direction and amount. Thedirections of the magnetic fluxes on the two neighboring winding pillarsare opposite. The magnetic flux flowing out of any of the four windingsflows to the two neighboring winding pillars and the auxiliary pillarunit to form three closed magnetic flux loops. The air gap is disposedon the auxiliary pillar unit. Two windings of the two inductors of thefirst and second switching power conversion units are the two windingsof the magnetic component wound around the magnetic core assembly.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a schematic circuit diagram illustrating a conventionaltwo-phase buck circuit;

FIG. 2A is a schematic circuit diagram illustrating a first powerconversion circuit according to an embodiment of the present disclosure;

FIG. 2B is a schematic circuit diagram illustrating a second powerconversion circuit according to an embodiment of the present disclosure;

FIG. 3A and FIG. 3B are schematic oscillograms showing the drivingsignals of the switches of the first power conversion circuit withdifferent duty ratios;

FIG. 3C is a schematic oscillogram showing the driving signals of theswitches of the second power conversion circuit;

FIG. 4A is a schematic circuit diagram illustrating a first powerconversion system according to a first embodiment of the presentdisclosure;

FIG. 4B is a schematic oscillogram showing the switch driving signal andcorresponding voltage variation of FIG. 4A;

FIG. 5A is a schematic circuit diagram illustrating a first powerconversion system according to a second embodiment of the presentdisclosure;

FIG. 5B is a schematic oscillogram showing the switch driving signal andcorresponding voltage variation of FIG. 5A;

FIG. 5C is a schematic circuit diagram illustrating a second powerconversion system according to a third embodiment of the presentdisclosure;

FIG. 5D is a schematic circuit diagram illustrating a second powerconversion system according to a fourth embodiment of the presentdisclosure;

FIG. 6A is a schematic circuit diagram illustrating a first powerconversion circuit according to a fifth embodiment of the presentdisclosure;

FIG. 6B is a schematic circuit diagram illustrating a power circuit anda precharge circuit that are applied to the first power conversioncircuit of the fifth embodiment shown in FIG. 6A;

FIG. 6C is a schematic circuit diagram illustrating a second powerconversion circuit according to a sixth embodiment of the presentdisclosure;

FIG. 6D shows the timing diagrams of the second power conversion circuitof FIG. 6C;

FIG. 7A is a schematic circuit diagram illustrating a first powerconversion circuit and clamping circuits according to a seventhembodiment of the present disclosure;

FIG. 7B is a schematic circuit diagram illustrating a first powerconversion circuit and clamping circuits according to an eighthembodiment of the present disclosure;

FIG. 7C is a schematic circuit diagram illustrating a first powerconversion circuit and clamping circuits according to a ninth embodimentof the present disclosure;

FIG. 7D is a schematic circuit diagram illustrating a second powerconversion circuit and clamping circuits according to a tenth embodimentof the present disclosure;

FIG. 7E is a schematic circuit diagram illustrating a second powerconversion circuit and clamping circuits according to an eleventhembodiment of the present disclosure;

FIG. 7F is a schematic circuit diagram illustrating a second powerconversion circuit and clamping circuits according to a twelfthembodiment of the present disclosure;

FIG. 8A is a schematic circuit diagram illustrating a first powerconversion circuit, a bootstrap circuit and driving circuits accordingto a thirteenth embodiment of the present disclosure;

FIG. 8B is a schematic circuit diagram illustrating a first powerconversion circuit, a bootstrap circuit and driving circuits accordingto a fourteenth embodiment of the present disclosure;

FIG. 8C is a schematic circuit diagram illustrating a second powerconversion circuit, bootstrap circuits and driving circuits according toa fifteenth embodiment of the present disclosure;

FIG. 9A is a schematic perspective view illustrating a part of themagnetic core assembly according to an embodiment of the presentdisclosure;

FIG. 9B schematically shows the direction of AC magnetic flux in themagnetic core assembly of FIG. 9A;

FIG. 9C is a schematic oscillogram showing the AC magnetic flux in themagnetic core assembly of FIG. 9A in one switching period;

FIG. 9D is a schematic perspective view illustrating a part of themagnetic core assembly according to another embodiment of the presentdisclosure;

FIG. 9E schematically shows the direction of AC magnetic flux in themagnetic core assembly of FIG. 9D;

FIG. 9F is a schematic perspective view illustrating a part of themagnetic core assembly according to further another embodiment of thepresent disclosure;

FIG. 10A is a schematic perspective view illustrating a part of themagnetic core assembly according to further another embodiment of thepresent disclosure;

FIG. 10B schematically shows the direction of AC magnetic flux in themagnetic core assembly of FIG. 10A;

FIG. 10C is a schematic oscillogram showing the AC magnetic flux in themagnetic core assembly of FIG. 10A in one switching period;

FIG. 10D, FIG. 10G, FIG. 10H and FIG. 10I are schematic perspectiveviews illustrating a part of different variants of the magnetic coreassembly of FIG. 10A;

FIG. 10E and FIG. 10F are vertical views of FIG. 10D which schematicallyshows two different winding manners of inductor;

FIG. 11A and FIG. 11B are schematic circuit diagrams illustrating aplurality of first power conversion circuits connected in parallel andinterleaved with each other;

FIG. 11C is a schematic circuit diagram illustrating a plurality ofsecond power conversion circuits connected in parallel and interleavedwith each other;

FIG. 12 is schematic circuit diagram illustrating a power conversionsystem including two first power conversion circuits;

FIG. 13A and FIG. 13B are schematic circuit diagrams illustrating aprecharge circuit of the power conversion system of FIG. 12;

FIG. 14 is a schematic circuit diagrams illustrating a bootstrap circuitof the power conversion system of FIG. 12;

FIG. 15 is schematic circuit diagram illustrating a power conversionsystem including two second power conversion circuits; and

FIG. 16 is a schematic circuit diagram illustrating a precharge circuitof the power conversion system of FIG. 15.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

The present disclosure will now be described more specifically withreference to the following embodiments. It is to be noted that thefollowing descriptions of preferred embodiments of this disclosure arepresented herein for purpose of illustration and description only. It isnot intended to be exhaustive or to be limited to the precise formdisclosed.

FIG. 2A is a schematic circuit diagram illustrating a first powerconversion circuit according to an embodiment of the present disclosure.FIG. 3A and FIG. 3B are schematic oscillograms showing the drivingsignals of the switches of the first power conversion circuit withdifferent duty ratios. FIG. 4A is a schematic circuit diagramillustrating a first power conversion system according to a firstembodiment of the present disclosure. FIG. 4B is a schematic oscillogramshowing the switch driving signal and corresponding voltage variation ofFIG. 4A. FIG. 5A is a schematic circuit diagram illustrating a firstpower conversion system according to a second embodiment of the presentdisclosure. FIG. 5B is a schematic oscillogram showing the switchdriving signal and corresponding voltage variation of FIG. 5A. As shownin FIG. 4A and FIG. 5A, the first power conversion system of the presentdisclosure includes a first power conversion circuit shown in FIG. 2A, apower circuit and at least one precharge circuit.

The first power conversion circuit includes an input port, an outputport, N switching power conversion units and N−1 storage device(s),where N is a positive integer larger than or equal to 2. The input portand the output port are configured to receive an input voltage Vin andgenerate an output voltage Vo respectively. Each of the N switchingpower conversion units includes a first switch and a second switchserially connected to each other. The first and second switches have aswitching period, and the first and second switches operate periodicallyaccording to the switching period. The switching period has a dutyratio. In addition, the first switch of the first switching powerconversion unit is connected to the input port, and the first switch ofother switching power conversion unit is serially connected to the firstswitch of the preceding switching power conversion unit in sequence. TheN−1 storage device is serially connected between the input and outputports. Two ends of each storage device have a first node and a secondnode respectively. There is n first switch between the (n)th storagedevice and the input port, where n is a positive integer larger than orequal to 1 and smaller than or equal to N−1. For example but notexclusively, the storage device is a capacitor. The storage device isconfigured to divide the input voltage. During one switching period, thestorage device stores the energy and transmits the energy to the outputport, and the energy stored by the storage device is proportional to theduty ratio. In an embodiment, the power conversion circuit furtherincludes a controller 10. The controller 10 is configured to output atleast two control signals PWM1 and PWM2 for controlling the switches ofthe switching power conversion units of the first power conversioncircuit. According to above descriptions, it is noted that the firstpower conversion circuit of the present disclosure is a multi-phase buckconverter with extended duty ratio. Compared with the conventional buckcircuit under the same input and output conditions, the first powerconversion circuit of the present disclosure can increase the duty ratioand reduce the amount of voltage jump while turning on or off switches.Therefore, the switching loss is reduced, and the efficiency isimproved.

The first power conversion system further includes a power circuit. Thepower circuit is electrically connected to the first power conversioncircuit for receiving the input voltage Vin, and the power circuitincludes a magnetic element T1. The magnetic element T1 is for examplebut not limited to an inductor or a transformer. In an embodiment, thepower circuit further outputs a supply voltage Vcc to the powerconversion circuit so as to supply power for the control and drivingchips in the power conversion circuit.

The first power conversion system further includes N−1 prechargecircuit. The N−1 precharge circuit is corresponding to the N−1 storagedevice one-to-one so as to charge the storage device. Each of the N−1precharge circuit includes a winding and a rectifier filter circuitconnected to each other. The winding is coupled to the magnetic elementT1 for receiving a conversion voltage. The output of the rectifierfilter circuit is electrically connected to the first and second nodesat two ends of the corresponding storage device. Consequently, therectifier filter circuit receives the conversion voltage and outputs acharge voltage to the corresponding storage device. In addition, theturns ratio of the winding of the precharge circuit configured forcharging the (n)th storage device to the magnetic element is (N−n):N.

Therefore, before the first power conversion circuit performs thevoltage conversion, the voltages on the magnetic element T1 of the powercircuit and the precharge circuit are utilized to precharge the storagedevice. Accordingly, the first power conversion circuit enters the softswitching state of the output voltage, which means that the terminalvoltage stress on the second switch is low when the first switch isturned on. Consequently, it is allowed to employ a switch component withlow withstanding voltage as the second switch so that the cost isreduced. Moreover, the switch component with low withstanding voltagehas low conducting inner resistance, which can improve the powerconversion efficiency and reduce the loss.

In addition, the specific topologies of the power circuit and theprecharge circuit may be varied corresponding to the type of powercircuit.

In an embodiment, the power circuit may be a buck circuit. As shown inFIG. 4A, the power circuit 21 includes the magnetic element T1, a fourthswitch S1 and a fifth switch S2. One terminal of the fourth switch S1 iselectrically connected to the input port, and the other terminal of thefourth switch S1 is connected to one terminal of the fifth switch S2 andone terminal of the magnetic element T1. The other terminal of the fifthswitch S2 is grounded, and the other terminal of the magnetic element T1is connected to the positive terminal of the supply voltage Vcc. Thefourth switch S1 and the fifth switch S2 are turned on by complementarysignals. In this embodiment, in each precharge circuit 31, the windingT2 has a first terminal T2 a and a second terminal T2 b, and therectifier filter circuit includes a first diode D1, a first capacitorC1, a second diode D2 and a second capacitor C2. The first terminal T2 aof the winding T2 is connected to the positive electrode of the firstdiode D1 and the negative electrode of the second diode D2. The secondterminal T2 b of the winding T2 is connected to the negative electrodeof the first capacitor C1 and the positive electrode of the secondcapacitor C2. The negative electrode of the first diode D1 and thepositive electrode of the first capacitor C1 are electrically connectedto the corresponding first node SWA. The positive electrode of thesecond diode D2 and the negative electrode of the second capacitor C2are electrically connected to the corresponding second node SWB.Consequently, the precharge for the storage device Cb can be realized.In fact, through adjusting the capacitance of the first and secondcapacitors C1 and C2, the charge current outputted from the rectifierfilter circuit 31 to the storage device Cb can be limited, therebyachieving the current limiting function. However, the way for limitingthe charge current is not limited thereto. In an embodiment, therectifier filter circuit 31 further includes a first resistor R1 and asecond resistor R2. One terminal of the first resistor R1 is connectedto the negative electrode of the first diode D1 and the positiveelectrode of the first capacitor C1, the other terminal of the firstresistor R1 is connected to the corresponding first node SWA. Oneterminal of the second resistor R2 is connected to the positiveelectrode of the second diode D2 and the negative electrode of thesecond capacitor C2, and the other terminal of the second resistor R2 isconnected to the corresponding second node SWB. Therefore, the first andsecond resistors R1 and R2 can work as current limiting resistors forlimiting the charge current provided to the storage device Cb. Inaddition, in an embodiment, the power circuit 21 further includes acapacitor Cvcc. One terminal of the capacitor Cvcc is connected to theother terminal of the magnetic element T1 (i.e., the positive terminalof the supply voltage Vcc), and the other terminal of the capacitor Cvccis grounded.

In another embodiment, the power circuit may be a flyback circuit. Asshown in FIG. 5A, the power circuit 22 includes the magnetic element T1and a sixth switch S3 connected in series. In each precharge circuit 32,the winding T3 is positively coupled to the magnetic element T1. Thefirst terminal of the winding T3 is connected to the positive electrodeof the third diode D3. The negative electrode of the third diode D3 isconnected to the positive electrode of the third capacitor C3 and iselectrically connected to the corresponding first node SWA. The secondterminal of the winding T3 is connected to the negative electrode of thethird capacitor C3 and is electrically connected to the second node SWB.Consequently, the precharge for the storage device Cb can be realized.In an embodiment, the rectifier filter circuit 32 further includes athird resistor R3 and a fourth resistor R4. One terminal of the thirdresistor R3 is connected to the negative electrode of the third diode D3and the positive electrode of the third capacitor C3, and the otherterminal of the third resistor R3 is connected to the correspondingfirst node SWA. One terminal of the fourth resistor R4 is connected tothe second terminal of the winding T3 and the negative electrode of thethird capacitor C3, and the other terminal of the fourth resistor R4 isconnected to the corresponding second node SWB. Therefore, the third andfourth resistors R3 and R4 can work as current limiting resistors forlimiting the charge current provided to the storage device Cb. In anembodiment, the power circuit 22 further includes a winding T4, a fourthdiode D4 and a capacitor Cvcc. One terminal of the winding T4 isconnected to the positive electrode of the fourth diode D4, the negativeelectrode of the fourth diode D4 is connected to one terminal of thecapacitor Cvcc and the power conversion circuit, and the other terminalof the winding T4 is connected to the other terminal of the capacitorCvcc and is grounded. Consequently, through the winding T4 negativelycoupled to the magnetic element T1, the supply voltage Vcc is generatedand is supplied to the power conversion circuit.

The actual implementation of the first power conversion circuit with Nequal to 2 is exemplified as follows according to the embodiments shownin FIG. 4A and FIG. 5A.

In the first embodiment shown in FIG. 4A, N equals 2, and the powerconversion circuit 11 includes two switching power conversion units andone storage device. The storage device is the capacitor Cb, and thereare the first node SWA and the second node SWB at the two ends of thecapacitor Cb respectively. The first switching power conversion unitincludes a first switch M11, a second switch M21 and an inductor L1. Thesecond switching power conversion unit includes a first switch M12, asecond switch M22 and an inductor L2. Please refer to FIG. 3A and FIG.3B, Ts is the switching period, and D is the duty ratio of the switchingperiod. FIG. 3A and FIG. 3B shows the switch driving signals of thepower conversion circuit 11 with D smaller than 50% and D larger than50% respectively. The control sequences of the first switches M11 andM12 are 180 degrees out of phase with respect to each other. The drivingsignals of the first and second switches M11 and M21 are complementaryto each other, and the driving signals of the first and second switchesM12 and M22 are complementary to each other.

The winding T2 of the precharge circuit 31 has the first terminal T2 aand the second terminal T2 b, and the turns ratio of the magneticelement T1 of the power circuit 21 to the winding T2 is 2:1. Pleaserefer to the oscillogram shown in FIG. 4B, where Daux is the duty ratioof the auxiliary power. When the fourth switch S1 is turned on and thefifth switch S2 is turned off, the voltage VT1 on the magnetic elementT1 equals Vin−Vcc, and the voltage VT2 on the winding T2 equals(Vin−Vcc)/2. Meanwhile, the potential at the first terminal T2 a ispositive, the potential at the second terminal T2 b is negative, and thefirst diode D1 is turned on. Therefore, the voltage VC1 on the firstcapacitor C1 equals (Vin−Vcc)/2. On the contrary, when the fourth switchS1 is turned off and the fifth switch S2 is turned on, the voltage VT1on the magnetic element T1 equals −Vcc. Meanwhile, the potential at thefirst terminal T2 a is negative, the potential at the second terminal T2b is positive, and the second diode D2 is turned on. Therefore, thevoltage VC2 on the second capacitor C2 equals Vcc/2. From above, it isnoted that the superposition voltage (equals Vin/2) on the two ends ofthe first and second capacitors C1 and C2 charge the capacitor Cbthrough the first and second resistors R1 and R2, which makes thevoltage on the capacitor Cb equal to Vin/2. Moreover, when the firstswitch M11 is turned on, the voltage stress on the second switches M21and M22 equals the difference between the input voltage Vin and thevoltage on the capacitor Cb (i.e., Vin−Vin/2=Vin/2). Since the voltagestress is low, it is allowed to employ the switches with lowwithstanding voltage as the second switches M21 and M22.

In the second embodiment shown in FIG. 5A, N equals 2, the powerconversion circuit 11 is similar to the power conversion circuit 11 ofFIG. 2A and FIG. 4A, and the detailed description thereof is omittedherein. The turns ratio of the magnetic element T1 of the power circuit22 to the winding T3 of the precharge circuit 32 is 2:1, and the windingT3 is positively coupled to the magnetic element T1. Please refer to theoscillogram shown in FIG. 5B. When the sixth switch S3 is turned on, thevoltage VT1 on the magnetic element T1 equals Vin, the voltage on thewinding T3 equals Vin/2, and the third diode D3 is turned on. Therefore,the voltage VC3 on the third capacitor C3 equals Vin/2. When the sixthswitch S3 is turned off, the supply voltage Vcc is provided through thenegative coupling between the winding T4 and the magnetic element T1.Meanwhile, the voltage VC3 on the third capacitor C3 charges thecapacitor Cb through the third resistor R3 and the fourth resistor R4,which makes the voltage on the capacitor Cb equal to Vin/2. Moreover,when the first switch M11 is turned on, the voltage stress on the secondswitches M21 and M22 equals the difference between the input voltage Vinand the voltage on the capacitor Cb (i.e., Vin−Vin/2=Vin/2). Since thevoltage stress is low, it is allowed to employ the switches with lowwithstanding voltage as the second switches M21 and M22.

FIG. 2B is a schematic circuit diagram illustrating a second powerconversion circuit according to an embodiment of the present disclosure.FIG. 3C is a schematic oscillogram showing the driving signals of theswitches of the second power conversion circuit. FIG. 5C is a schematiccircuit diagram illustrating a second power conversion system accordingto a third embodiment of the present disclosure. FIG. 5D is a schematiccircuit diagram illustrating a second power conversion system accordingto a fourth embodiment of the present disclosure. As shown in FIG. 5Cand FIG. 5D, the second power conversion system of the presentdisclosure includes a second power conversion circuit shown in FIG. 2B,a power circuit and at least one precharge circuit.

The second power conversion circuit includes an input port, an outputport, N switching power conversion units and N storage devices, where Nis a positive integer larger than or equal to 2. The input port and theoutput port are configured to receive an input voltage Vin and generatean output voltage Vo respectively. Each of the N switching powerconversion units includes a first switch, a second switch and a thirdswitch. The first, second and third switches operate periodicallyaccording to a switching period. The switching period has a duty ratio.In addition, the first terminal of the first switch is electricallyconnected to the input port, and the first terminal of the storagedevice is electrically connected to the second terminal of the firstswitch. The second terminal of the storage device is electricallyconnected to the second terminal of the second switch and one terminalof the third switch, and the other terminal of the third switch isgrounded. The first terminal of the second switch is electricallyconnected to the second terminal of the first switch of anotherswitching power conversion unit.

The second power conversion system further includes a power circuit. Thepower circuit is electrically connected to the second power conversioncircuit for receiving the input voltage Vin, and the power circuitincludes a magnetic element T1. The magnetic element T1 is for examplebut not limited to an inductor or a transformer. In an embodiment, thepower circuit further outputs a supply voltage Vcc to the powerconversion circuit so as to supply power for the control and drivingchips in the power conversion circuit. As shown in FIG. 5C and FIG. 5D,the power circuit may be the flyback circuit shown in FIG. 5A, and thedetailed description thereof is omitted herein.

The second power conversion system further includes at least oneprecharge circuit. The number of the precharge circuit is larger than orequal to 1 and is smaller than or equal to N. Each precharge circuitincludes a winding and a rectifier filter circuit connected to eachother. The winding is coupled to the magnetic element T1 for receiving aconversion voltage. The output of the rectifier filter circuit iselectrically connected to the first and second nodes at two ends of thecorresponding storage device respectively. Consequently, the rectifierfilter circuit receives the conversion voltage and outputs a chargevoltage to the corresponding storage device. In addition, the turnsratio of the winding of the precharge circuit configured for chargingthe storage device to the magnetic element is 1:2.

In an embodiment, the second power conversion system may include oneprecharge circuit, and the one precharge circuit outputs charge voltageto the N storage devices. In another embodiment, the second powerconversion system may include N precharge circuits, and the N prechargecircuits are corresponding to the N storage devices one-to-one so as tocharge the corresponding storage device respectively. In further anotherembodiment, some storage devices of the N storage devices share oneprecharge circuit. Taking the second power conversion circuit includingtwo switching power conversion units as an example, the prechargecircuit therefor is exemplified as follows. Further, the second powerconversion circuit includes two storage device, which are storagecapacitors Cb10 and Cb11.

In an embodiment, as shown in FIG. 5C, the second power conversionsystem includes two precharge circuits 36 and 37. In these two prechargecircuits 36 and 37, two windings T31 and T32 are both positively coupledto the magnetic element T1, and each of the two windings T31 and T32 hasa first terminal and a second terminal. One rectifier filter circuitincludes a third diode D31 and a third capacitor C31, and the otherrectifier filter circuit includes a third diode D32 and a thirdcapacitor C32. The first terminal of the winding T31 is connected to thepositive electrode of the third diode D31, and the negative electrode ofthe third diode D31 is connected to the positive electrode of the thirdcapacitor C31 and is electrically connected to the first node SWE of thestorage device Cb10. The second terminal of the winding T31 iselectrically connected to the second node SWF of the storage deviceCb10. Consequently, the precharge for the storage device Cb10 can berealized. The first terminal of the winding T32 is connected to thepositive electrode of the third diode D32, and the negative electrode ofthe third diode D32 is connected to the positive electrode of the thirdcapacitor C32 and is electrically connected to the first node SWG of thestorage device Cb11. The second terminal of the winding T32 iselectrically connected to the second node SWH of the storage deviceCb11. Consequently, the precharge for the storage device Cb11 can berealized.

In another embodiment, the second power conversion system includes oneprecharge circuit 35. In the precharge circuit 35, the winding T3 ispositively coupled to the magnetic element T1, the winding T3 has afirst terminal and a second terminal, and the rectifier filter circuitincludes a third diode D3 and a third capacitor C3. The first terminalof the winding T3 is connected to the positive electrode of the thirddiode D3, the negative electrode of the third diode D3 is connected tothe positive electrode of the third capacitor C3, and the two ends ofthe third capacitor C3 are electrically connected to two sets ofisolation diodes (D73, D74) and (D71, D72) respectively. The thirdcapacitor C3 precharges the storage devices Cb10 and Cb11 through thetwo sets of isolation diodes. In particular, the positive electrode ofthe third capacitor C3 is electrically connected to the positiveelectrodes of the two isolation diodes D71 and D73, and the negativeelectrodes of the two isolation diodes D71 and D73 are electricallyconnected to the corresponding first nodes SWE and SWG respectively. Thenegative electrode of the third capacitor C3 (i.e., the second terminalof the winding T3) is electrically connected to the positive electrodesof the two isolation diodes D72 and D74, and the negative electrodes ofthe two isolation diodes D72 and D74 are electrically connected to thecorresponding second nodes SWF and SWH respectively. Consequently, theprecharge for the storage devices Cb10 and Cb11 can be realized.

The actual implementation of the second power conversion circuit with Nequal to 2 is exemplified as follows according to the embodiments shownin FIG. 5C and FIG. 5D.

In the third embodiment shown in FIG. 5C, N equals 2, and the secondpower conversion circuit 13 includes two switching power conversionunits and two storage devices. The first switching power conversion unitincludes a first switch S11, a second switch S22, a third switch SR1 andan inductor L1. The second switching power conversion unit includes afirst switch S12, a second switch S21, a third switch SR2 and aninductor L2. The storage devices are the capacitors Cb10 and Cb11. Thereare the first node SWE and the second node SWF at two ends of thecapacitor Cb10 respectively, and there are the first node SWG and thesecond node SWH at two ends of the capacitor Cb11 respectively. Pleaserefer to FIG. 3C, where Ts is the switching period, and D is the dutyratio of the switching period. The first switch S11 and the secondswitch S22 are turned on and off simultaneously, and the first switchS12 and the second switch S21 are turned on and off simultaneously. Thecontrol sequences of the first switches S11 and S12 are 180 degrees outof phase with respect to each other. The driving signals of the firstand third switches S11 and SR1 are complementary to each other, and thedriving signals of the first and third switches S12 and SR2 arecomplementary to each other.

The turns ratio of the magnetic element T1 of the power circuit 22 tothe winding T31 of the precharge circuit 36 is 2:1, and the turns ratioof the magnetic element T1 of the power circuit 22 to the winding T32 ofthe precharge circuit 37 is 2:1. Moreover, the winding T31 is positivelycoupled to the magnetic element T1, and the winding T32 is positivelycoupled to the magnetic element T1. Please refer to the oscillogramshown in FIG. 5B. When the sixth switch S3 is turned on, the voltage VT1on the magnetic element T1 equals Vin, and the voltages on the windingsT31 and T32 both equal Vin/2, and the third diodes D31 and D32 areturned on. Therefore, the voltages VC31 and VC32 on the third capacitorsC31 and C32 respectively both equal Vin/2. When the sixth switch S3 isturned off, the supply voltage Vcc is provided through the negativecoupling between the winding T4 and the magnetic element T1. Meanwhile,the voltage VC31 on the third capacitor C31 charges the capacitor Cb10through the third resistor R31 and the fourth resistor R41, which makesthe voltage on the capacitor Cb10 equal to Vin/2. Similarly, the voltageVC32 on the third capacitor C32 charges the capacitor Cb11 through thethird resistor R32 and the fourth resistor R42, which makes the voltageon the capacitor Cb11 equal to Vin/2. Moreover, when the first switchS11 and the second switch S22 are turned on, the voltage stress on thethird switch SR1 equals the difference between the input voltage Vin andthe voltage on the capacitor Cb10 (i.e., Vin−Vin/2=Vin/2). When thefirst switch S12 and the second switch S21 are turned on, the voltagestress on the third switch SR2 equals the difference between the inputvoltage Vin and the voltage on the capacitor Cb11 (i.e.,Vin−Vin/2=Vin/2). Since the voltage stress is low, it is allowed toemploy the switches with low withstanding voltage as the third switchesSR1 and SR2.

In the fourth embodiment shown in FIG. 5D, N equals 2. The powerconversion circuit 13 is similar to the power conversion circuit 13 ofFIG. 2B and FIG. 5C, and the detailed description thereof is omittedherein. The turns ratio of the magnetic element T1 of the power circuit22 to the winding T3 of the precharge circuit 35 is 2:1, and the windingT3 is positively coupled to the magnetic element T1. Please refer to theoscillogram shown in FIG. 5B. With the same work principle, the voltageVC3 on the third capacitor C3 equals Vin/2. The voltage VC3 charges thecapacitor Cb10 through the third resistor R3, the fourth resistor R4 andthe isolation diodes D71 and D72, which makes the voltage on thecapacitor Cb10 equal to Vin/2. The voltage VC3 charges the capacitorCb11 through the third resistor R3, the fourth resistor R4 and theisolation diodes D73 and D74, which makes the voltage on the capacitorCb11 equal to Vin/2. The other work principle is the same as that shownin FIG. 5C, and the detailed description thereof is omitted herein.

Naturally, in the above-mentioned embodiments, N may be a positiveinteger larger than or equal to 2 and is not limited to 2. Namely, thepower conversion circuit may be a circuit with two or more phases. Inorder to clarify the variation of the power conversion system as Nincreases, the power conversion system with N equal to 3 is exemplifiedas follows.

FIG. 6A is a schematic circuit diagram illustrating a first powerconversion circuit according to a fifth embodiment of the presentdisclosure. FIG. 6B is a schematic circuit diagram illustrating a powercircuit and a precharge circuit that are applied to the first powerconversion circuit of the fifth embodiment shown in FIG. 6A. As shown inFIG. 6A and FIG. 6B, N equals 3, and the first power conversion circuit12 includes three switching power conversion units and two storagedevices. The two storage devices are capacitors Cb1 and Cb2respectively. Two ends of the capacitor Cb1 have a first node SWA and asecond node SWB respectively, and two ends of the capacitor Cb2 have afirst node SWC and a second node SWD respectively. The first switchingpower conversion unit includes a first switch M11, a second switch M21and an inductor L1, the second switching power conversion unit includesa first switch M12, a second switch M22 and an inductor L2, and thethird switching power conversion unit includes a first switch M13, asecond switch M23 and an inductor L3. The controller 10 generates twocontrol signals PWM1 and PWM2, and the two control signals are 180degrees out of phase with respect to each other. The control signal PWM1is utilized to control the on and off of the first switches M11 and M13,and the control signal PWM2 is utilized to control the on and off of thefirst switch M12. The control signal of the second switches M21 and M23is complementary to the control signal PWM1, and the control signal ofthe second M22 is complementary to the control signal PWM2. This controlmethod can also be applied to the power conversion circuit including Nswitching power conversion units and N−1 storage devices connected inseries. In particular, in the odd-numbered switching power conversionunits, the first switch is controlled by the control signal PWM1, andthe control signal of the second switch is complementary to the controlsignal PWM1. In the even-numbered switching power conversion units, thefirst switch is controlled by the control signal PWM2, and the controlsignal of the second switch is complementary to the control signal PWM2.

The circuit structure of the power circuit 22 and the precharge circuit33 in the case that the power circuit is a flyback circuit isexemplified as follows, but not limited thereto. If the power circuit isa buck circuit, the circuit structure of the power circuit and themulti-branch precharge circuit can be derived and constructed accordingto the circuit structure shown in FIG. 4A. Please refer to FIG. 6B. Theturns ratio of the magnetic element T1 to the winding T31 of the firstprecharge circuit 33 is 3:2, and the winding T31 is positively coupledto the magnetic element T1. The turns ratio of the magnetic element T1to the winding T32 of the second precharge circuit 34 is 3:1, and thewinding T32 is positively coupled to the magnetic element T1. The outputof the first precharge circuit 33 is electrically connected to the firstand second nodes SWA and SWB at two ends of the capacitor Cb1respectively. The output of the second precharge circuit 34 iselectrically connected to the first and second nodes SWC and SWD at twoends of the capacitor Cb2 respectively. Therefore, the third capacitorC31 of the first precharge circuit 33 can charge the capacitor Cb1 to2Vin/3 through the third resistor R31 and the fourth resistor R41, andthe third capacitor C32 of the second precharge circuit 34 can chargethe capacitor Cb2 to Vin/3 through the third resistor R32 and the fourthresistor R42. Moreover, when the first switches M11 and M13 are turnedon, or when the first switch M12 is turned on, the voltage stress on thesecond switches M21, M22 and M23 equals the difference between the inputvoltage Vin and the voltage on the capacitor Cb1 (i.e.,Vin−2Vin/3=Vin/3). Since the voltage stress is low, it is allowed toemploy the switches with low withstanding voltage as the second switchesM21, M22 and M23.

FIG. 6C is a schematic circuit diagram illustrating a second powerconversion circuit according to a sixth embodiment of the presentdisclosure. FIG. 6D shows the timing diagrams of the second powerconversion circuit of FIG. 6C. As shown in FIG. 6C, N equals 3, thesecond power conversion circuit 14 includes three switching powerconversion units and three storage devices. The three storage devicesare capacitors Cb10, Cb11 and Cb12 respectively. Two ends of thecapacitor Cb10 have a first node SWE and a second node SWF respectively,two ends of the capacitor Cb11 have a first node SWG and a second nodeSWH respectively, and two ends of the capacitor Cb12 have a first nodeSWI and a second node SWJ respectively. The first switching powerconversion unit includes a first switch S11, a second switch S22, athird switch SR1 and an inductor L1. The second switching powerconversion unit includes a first switch S12, a second switch S23, athird switch SR2 and an inductor L2. The third switching powerconversion unit includes a first switch S13, a second switch S21, athird switch SR3 and an inductor L3. Please refer to FIG. 6D, where Tsis the switching period, and D is the duty ratio of the switchingperiod. FIG. 6D shows the switch driving signals of the second powerconversion circuit 14 of FIG. 6C with D smaller than 50%. In eachswitching power conversion unit, the control signals of the first andsecond switches are the same, and the control signal of the third switchis complementary to that of the second switch. Further, the controlsignals of the first switches of the three switching power conversionunits are 120 degrees out of phase with respect to each other insequence. Namely, the controller 10 generates three control signalsPWM1, PWM2 and PWM3, which are 120 degrees out of phase with respect toeach other in sequence. This control method can also be applied to thesecond power conversion circuit including N switching power conversionunits. In particular, the N first switches of the N switching powerconversion units are controlled by N control signals respectively, andthe N control signals are 360/N degrees out of phase with respect toeach other in sequence. In each switching power conversion unit, thecontrol signals of the first and second switches are the same, and thecontrol signal of the third switch is complementary to that of the firstswitch.

For realizing the precharge for the storage device of the second powerconversion circuit of FIG. 6C, in an embodiment, the second powerconversion system may include three precharge circuits. The prechargecircuit is similar to that shown in FIG. 5C, namely the three prechargecircuits are utilized to charge the three storage devices, such as thecapacitors Cb10, Cb11 and Cb12, respectively. Each precharge circuitincludes a winding positively coupled to the magnetic element T1 of thepower circuit 22, and the turns ratio of the magnetic element T1 to eachwinding is 2:1. In another embodiment, the second power conversionsystem may include one precharge circuit, and the precharge circuit issimilar to that shown in FIG. 5D. Different from the precharge circuitshown in FIG. 5D, the precharge circuit in this embodiment utilizesthree sets of isolation diodes to form three sets of charging outputterminals for charging the storage devices Cb10, Cb11 and Cb12respectively. In addition, the winding of the precharge circuit ispositively coupled to the magnetic element T1 of the power circuit 22,and the turns ratio of the magnetic element T1 to the winding is 2:1. Infurther another embodiment, the second power conversion system mayinclude two precharge circuits. One of the two precharge circuits issimilar to that shown in FIG. 5C, and the other precharge circuit issimilar to that shown in FIG. 5D, so as to charge the storage devicesCb10, Cb11 and Cb12. In the said three embodiments, the work principlethereof is the same as that shown in FIG. 5C and FIG. 5D, thus isomitted herein.

In the power conversion system, the power in the precharge circuit isprovided from the magnetic element of the power circuit. There is avoltage on the magnetic element, and the magnetic element is coupled tothe winding of the precharge circuit so as to provide the power for theprecharge circuit. In addition, all the diodes of the precharge circuitsof FIG. 4A, FIG. 5A, FIG. 5C, FIG. 5D and FIG. 6B (e.g., the diodes D1and D2 of FIG. 4A, the diode D3 of FIG. 5A, the diodes D31 and D32 ofFIG. 5C, the diode D3 of FIG. 5D and the diodes D31 and D32 of FIG. 6B)can be replaced by controllable switches.

For the first and second power conversion circuits, due to the existenceof storage devices, the circuit wiring is complicated, and the loopformed by the storage device and switch component is large. Accordingly,the peak voltage generated while turning on or off switch becomeslarger, thus there is a need of providing a clamping circuit to protectthe grounded switch. In order to prevent the peak voltage generatedwhile turning on or off switch from damaging the grounded switch of theswitching power conversion unit, the clamping circuit is disposed at twoends of the grounded switch. The clamping circuit includes an absorbingcircuit and a discharging circuit. The absorbing circuit is configuredto absorb the peak voltage on the grounded switch so as to protect thegrounded switch. The discharging circuit feeds the power absorbed by theabsorbing circuit back to the storage component of the circuit, so as toreduce the power loss. In particular, in an embodiment, the powerconversion system further includes N clamping circuits. Each of the Nclamping circuits is connected to the corresponding grounded switch ofthe switching power conversion unit so that the voltage on thecorresponding grounded switch is clamped.

FIG. 7A is a schematic circuit diagram illustrating a first powerconversion circuit and clamping circuits according to a seventhembodiment of the present disclosure. FIG. 7B is a schematic circuitdiagram illustrating a first power conversion circuit and clampingcircuits according to an eighth embodiment of the present disclosure. Asshown in FIG. 7A and FIG. 7B, each of the N switching power conversionunits of the first power conversion circuit is corresponding to oneclamping circuit. Therefore, for example, the voltage on the secondswitches M21 and M22 are clamped. When the duty ratio of the switchingperiod of the first switch is smaller than or equal to 50%, as shown inFIG. 7A, each clamping circuit includes an absorbing circuit and adischarging circuit. The absorbing circuit includes an absorbing diodeand an absorbing capacitor, and the discharging circuit includes adischarging diode. The absorbing diode is connected to the absorbingcapacitor in series. The positive electrode of the absorbing diode isconnected to one terminal of the corresponding second switch, oneterminal of the absorbing capacitor is connected to the negativeelectrode of the absorbing diode, and the other terminal of theabsorbing capacitor is connected to the other terminal of thecorresponding second switch. One terminal of the discharging circuit isconnected to the negative electrode of the absorbing diode, and theother terminal of the discharging circuit is connected to thecorresponding first node. When the duty ratio is larger than 50%, asshown in FIG. 7B, the connection relations of the negative electrode ofthe discharging diode of some clamping circuits are different from thatof the clamping circuit with the duty ratio smaller than or equal to50%. In specific, in the case that the duty ratio is larger than 50%,the negative electrode of the discharging diode of the first clampingcircuit is connected to the corresponding first node, and the negativeelectrodes of the discharging diodes of other clamping circuits are allconnected to the positive input port of the power conversion circuit.

In the seventh embodiment shown in FIG. 7A, N equals 2, and the dutyratio of the switching period of the first switch is smaller than orequal to 50%. The power conversion circuit is the same as that shown inFIG. 2A. With regard to the first clamping circuit, which includes anabsorbing circuit and a discharging circuit, the absorbing circuitincludes an absorbing diode D41 and an absorbing capacitor C41 connectedin series. The negative electrode of the absorbing diode D41 isconnected to the absorbing capacitor C41. The absorbing circuit isconnected to the two ends of the second switch M21 in parallel. Further,the absorbing circuit is disposed near the second switch M21 on thelayout of the printed circuit board, so as to achieve the shortestwiring path between the absorbing circuit and the second switch M21. Inaddition, in the first clamping circuit, the discharging circuitincludes a discharging diode D51. The positive electrode of thedischarging diode D51 is connected to the negative electrode of theabsorbing diode D41, and the negative electrode of the discharging diodeD51 is connected to the first node SWA. When the first switch M11 isturned on, there is a voltage drop of Vin/2 on the two ends of thesecond switch M21 instantaneously, and the voltage drop includes a peakvoltage generated at the conduction moment. Meanwhile, the absorbingdiode D41 is turned on, the absorbing capacitor C41 absorbs the peakvoltage generated at the conduction moment of the first switch M11. Whenthe first switch M11 is turned off and the second switch M21 is turnedon, the drain-source voltage Vds on the two ends of the second switchM21 is decreased, the absorbing diode D41 is cut off inversely, and thedischarging diode D51 of the discharging circuit is turned on.Consequently, the power on the absorbing capacitor C41 is discharged andfed back to the storage device Cb of the power conversion circuitthrough the discharging diode D51.

With regard to the second clamping circuit, which also includes anabsorbing circuit and a discharging circuit, the absorbing circuitincludes an absorbing diode D42 and an absorbing capacitor C42 connectedin series. The negative electrode of the absorbing diode D42 isconnected to the absorbing capacitor C42. The absorbing circuit isconnected to the two ends of the second switch M22 in parallel. Further,the absorbing circuit is disposed near the second switch M22 on thelayout of the printed circuit board, so as to achieve the shortestwiring path between the absorbing circuit and the second switch M22. Inaddition, in the second clamping circuit, the discharging circuitincludes a discharging diode D52. The positive electrode of thedischarging diode D52 is connected to the negative electrode of theabsorbing diode D42, and the negative electrode of the discharging diodeD52 is connected to the first node SWA. When the first switch M12 isturned on, there is a voltage drop of Vin/2 on the two ends of thesecond switch M22 instantaneously, and the voltage drop includes a peakvoltage generated at the conduction moment. Meanwhile, the absorbingdiode D42 is turned on, the absorbing capacitor C42 absorbs the peakvoltage generated at the conduction moment of the first switch M12. Whenthe voltage on the absorbing capacitor C42 is larger than Vin/2, thedischarging diode D52 is turned on. Consequently, the power on theabsorbing capacitor C42 is discharged and fed back to the storage deviceCb of the power conversion circuit through the discharging diode D52.Therefore, the protection for the second switches M21 and M22 isrealized through the clamping circuits.

Usually, in the conventional buck circuit, the power on the absorbingcapacitor is fed back to the input capacitor of the converter circuit,and the voltage on the switch is clamped to Vin. However, in theembodiment of the present disclosure, the power on the absorbingcapacitor is fed back to the storage device Cb of the power conversioncircuit, which can reduce the loss of the peak energy and improves theefficiency of the power conversion circuit. Moreover, since the voltagedrop on the two ends of the storage device Cb equals Vin/2 during steadywork state, the voltage drops on the second switches M21 and M22 areclamped to Vin/2. Therefore, it is allowed to employ the switch with lowwithstanding voltage level as the second switch, which reduces the cost.

In the eighth embodiment of the present disclosure shown in FIG. 7B, Nequals 2, and the duty ratio of the switching period of the first switchis larger than 50%. The power conversion circuit is similar to thatshown in FIG. 2A. The work principle of the first clamping circuitprotecting the second switch M21 is similar to that shown in FIG. 7A,and the detailed description thereof is omitted herein. With regard tothe second clamping circuit of FIG. 7B, when the first switch M12 andthe second switch M21 are both turned on, there is a voltage drop of Vinon the two ends of the second switch M22 instantaneously at theconduction moment of the first switch M11. The voltage drop includes apeak voltage generated at the conduction moment. Meanwhile, theabsorbing diode D42 is turned on, the absorbing capacitor C42 absorbsthe peak voltage generated at the conduction moment of the first switchM11. When the first switch M12 is turned off and the second switch M22is turned on, the drain-source voltage Vds on the two ends of the secondswitch M22 is decreased, the absorbing diode D42 is cut off inversely,and the discharging diode D52 of the discharging circuit is turned on.Consequently, the power on the absorbing capacitor C42 is discharged andfed back to the input capacitor at the input port of the powerconversion circuit through the discharging diode D52.

In the embodiments shown in FIG. 7A and FIG. 7B, the mentioned clampingcircuit is DCD clamping circuit. For example, the absorbing capacitorC41 and the absorbing diode D41 are connected to the two ends of thesecond switch M21 in parallel, thus the absorbing loop has short pathand achieves good absorbing effect. However, in these embodiments, avoltage ripple is superimposed on the DC potential of the voltage ofVin/2 on the first node SWA, and the voltage ripple causes some energyloss when the power on the absorbing capacitor C41 is discharged to thestorage device Cb through the discharging diode D51. In anotherembodiment, in order to avoid the energy loss, a CDC clamping circuit isprovided and is applied to the first power conversion circuit of FIG.2A. The CDC clamping circuit replaces the DCD clamping circuit disposedat the two ends of the second switch M21 of the first switching powerconversion unit. The clamping circuit which is disposed at the two endsof the second switch of any other switching power conversion unit (e.g.,the second switch M22) is still DCD clamping circuit.

FIG. 7C is a schematic circuit diagram illustrating a first powerconversion circuit and clamping circuits according to a ninth embodimentof the present disclosure. In the embodiment shown in FIG. 7C, N equals2, and the power conversion circuit is the same as that of FIG. 2A. Thework principle of the second clamping circuit protecting the secondswitch M22 is similar to that shown in FIG. 7A and FIG. 7B, and thedetailed description thereof is omitted herein. As shown in FIG. 7C, atthe moment that the first switch M11 is turned on, there is a voltagedrop of Vin/2 on the two ends of the second switch M21 instantaneously,and the voltage drop includes a peak voltage generated at the conductionmoment. In this embodiment, a CDC clamping circuit is connected to thetwo ends of the second switch M21 in parallel, and the CDC clampingcircuit forms mirror symmetry relative to the storage device Cb, theinput capacitor Cin and the parasitic diode MD1 at the two ends of thefirst switch M11. The CDC clamping circuit includes an absorbing circuitthat includes an absorbing diode MD1′ and absorbing capacitors Cb′ andCin′. One terminal of the absorbing capacitor Cb′ is serially connectedto the positive electrode of the absorbing diode MD1′, and one terminalof the absorbing capacitor Cin′ is serially connected to the negativeelectrode of the absorbing diode MD1′. The absorbing circuit isconnected to the two ends of the second switch M21 in parallel. Further,the components of the absorbing circuit are disposed near the secondswitch M21 on the layout of the printed circuit board, so as to achievethe shortest wiring path. In this embodiment, there is no need todispose the discharging circuit. By connecting the positive and negativeelectrodes of the absorbing diode MD1′ to the first node and thepositive input port respectively, the energy absorption andlong-distance discharge can be realized by the switches and capacitorsof the power conversion circuit.

The work principle is illustrated as follows. At the moment that thefirst switch M11 is turned on, the peak voltage generated on the twoends of the second switch M21 is absorbed by the absorbing capacitorsCb′ and Cin′ of the CDC clamping circuit. Meanwhile, the absorbingcapacitors Cb′ and Cin′ discharges to the storage device Cb and theinput capacitor Cin. Consequently, the protection for the second switchM21 is realized. In addition, in this embodiment, the voltage drop onthe two ends of the absorbing capacitor Cin′ is clamped to Vin, and thevoltage drop on the two ends of the absorbing capacitor Cb′ is clampedto −Vin/2. Therefore, in this embodiment, the voltage drop on the twoends of the second switch M21 is clamped to substantially Vin/2, and itis allowed to employ the switch with low withstanding-voltage level asthe second switch M21. Moreover, in this embodiment, there is no furtherspecial requirements to the capacitances of the two capacitors Cb′ andCin′ except for absorbing power, which makes the design simpler andreduces the loss.

FIG. 7D is a schematic circuit diagram illustrating a second powerconversion circuit and clamping circuits according to a tenth embodimentof the present disclosure. FIG. 7E is a schematic circuit diagramillustrating a second power conversion circuit and clamping circuitsaccording to an eleventh embodiment of the present disclosure. FIG. 7Fis a schematic circuit diagram illustrating a second power conversioncircuit and clamping circuits according to a twelfth embodiment of thepresent disclosure. The clamping circuits of FIG. 7D, FIG. 7E and FIG.7F can be applied to the second power conversion circuit of FIG. 2B forclamping the voltage on the third switches SR1 and SR2. As shown in FIG.7D and FIG. 7E, each of the N switching power conversion units of thesecond power conversion circuit is corresponding to one clampingcircuit, and each clamping circuit includes an absorbing circuit and adischarging circuit. The absorbing circuit includes an absorbing diodeand an absorbing capacitor, and the discharging circuit includes adischarging diode. The absorbing diode is connected to the absorbingcapacitor in series. The positive electrode of the absorbing diode isconnected to one terminal of the corresponding third switch, oneterminal of the absorbing capacitor is connected to the negativeelectrode of the absorbing diode, and the other terminal of theabsorbing capacitor is connected to the other terminal of the thirdswitch and is grounded. One terminal of the discharging circuit isconnected to the negative electrode of the absorbing diode, and theother terminal of the discharging circuit is connected to thecorresponding first node.

In the embodiment shown in FIG. 7D, N equals 2. With regard to theclamping circuit corresponding to the first switching power conversionunit, the absorbing circuit includes an absorbing diode D43 and anabsorbing capacitor C43 connected in series. The negative electrode ofthe absorbing diode D43 is connected to the absorbing capacitor C43. Theabsorbing circuit is connected to the two ends of the third switch SR1in parallel. Further, the absorbing circuit is disposed near the thirdswitch SR1 on the layout of the printed circuit board, so as to achievethe shortest wiring path between the absorbing circuit and the thirdswitch SR1. The discharging circuit includes a discharging diode D53.The positive electrode of the discharging diode D53 is connected to thenegative electrode of the absorbing diode D43, and the negativeelectrode of the discharging diode D53 is connected to the first nodeSWG of the second switching power conversion unit. When the first switchS11 and the second switch S22 are turned on, there is a voltage drop ofVin/2 on the two ends of the third switch SR1 instantaneously, and thevoltage drop includes a peak voltage generated at the conduction moment.Meanwhile, the absorbing diode D43 is turned on, and the absorbingcapacitor C43 absorbs the peak voltage generated at the conductionmoment of the first switch S11 and the second switch S22. When thevoltage on the absorbing capacitor C43 is larger than Vin/2, thedischarging diode D53 is turned on. Consequently, the power on theabsorbing capacitor C43 is discharged and fed back to the storage deviceCb11 of the second switching power conversion unit through thedischarging diode D53. Since the voltage drop on the two ends of thestorage device Cb11 equals Vin/2 during steady work state, the voltagedrop on the third switch SR1 is clamped to Vin/2. Therefore, it isallowed to employ the switch with low withstanding-voltage level as thethird switch SR1.

With regard to the clamping circuit corresponding to the secondswitching power conversion unit, the absorbing circuit includes anabsorbing diode D44 and an absorbing capacitor C44 connected in series.The negative electrode of the absorbing diode D44 is connected to theabsorbing capacitor C44. The absorbing circuit is connected to the twoends of the third switch SR2 in parallel. Further, the absorbing circuitis disposed near the third switch SR2 on the layout of the printedcircuit board, so as to achieve the shortest wiring path between theabsorbing circuit and the third switch SR2. In addition, the dischargingcircuit includes a discharging diode D54. The positive electrode of thedischarging diode D54 is connected to the negative electrode of theabsorbing diode D44, and the negative electrode of the discharging diodeD54 is connected to the first node SWE of the first switching powerconversion unit. When the first switch S12 and the second switch S21 areturned on, there is a voltage drop of Vin/2 on the two ends of the thirdswitch SR2 instantaneously, and the voltage drop includes a peak voltagegenerated at the conduction moment. Meanwhile, the absorbing diode D44is turned on, and the absorbing capacitor C44 absorbs the peak voltagegenerated at the conduction moment of the first switch S12 and thesecond switch S21. When the voltage on the absorbing capacitor C44 islarger than Vin/2, the discharging diode D54 is turned on. Consequently,the power on the absorbing capacitor C44 is discharged and fed back tothe storage device Cb10 of the first switching power conversion unitthrough the discharging diode D54. Since the voltage drop on the twoends of the storage device Cb10 equals Vin/2 during steady work state,the voltage drop on the third switch SR2 is clamped to Vin/2. Therefore,it is allowed to employ the switch with low withstanding-voltage levelas the third switch SR2. Consequently, the protection for the thirdswitches SR1 and SR2 is realized. Since the peak energy absorbed by theabsorbing capacitors C43 and C44 is fed back to the storage devices Cb10and Cb11, the loss of the peak energy is reduced, and the efficiency ofthe power conversion circuit is improved.

In the embodiment shown in FIG. 7E, N equals 2, the clamping circuitscorresponding to the first and second switching power conversion unitsare similar to that of FIG. 7D except for the connection relations ofthe negative electrode of the discharging diode of the clamping circuit.Namely, the point of the discharging circuit feeding the absorbed peakenergy back to the storage component is different. Taking the clampingcircuit corresponding to the first switching power conversion unit as anexample, the negative electrode of the discharging diode D53 isconnected to the first node SWE. When the first switch S11 and thesecond switch S22 are turned on, the peak voltage is generated on thethird switch SR1 at the conduction moment. Meanwhile, the absorbingdiode D43 is turned on, and the absorbing capacitor C43 absorbs the peakvoltage. When the first and second switches S11 and S22 are turned offand the first and second switches S12 and S21 are turned on, theabsorbing diode D43 is cut off inversely, and the discharging diode D53of the discharging circuit is turned on. Consequently, the power on theabsorbing capacitor C43 is discharged and fed back to the storage deviceCb10 through the discharging diode D53. Since the voltage drop on thetwo ends of the storage device Cb10 equals Vin/2 during steady workstate, the voltage drop on the third switch SR1 is clamped to Vin/2.Therefore, it is allowed to employ the switch with lowwithstanding-voltage level as the third switch SR1. Similarly, thenegative electrode of the clamping circuit corresponding to the secondswitching power conversion unit is connected to the first node SWG, andthe work principle is substantially the same, thus the detaileddescription thereof is omitted herein.

In actual applications, the negative electrode of the discharging diodeof each clamping circuit is connected to the first node of thecorresponding switching power conversion unit or another switching powerconversion unit according to actual requirements, and is not limitedherein.

In the embodiments shown in FIG. 7D and FIG. 7E, a voltage ripple issuperimposed on the DC potential of the voltage of Vin/2 on the firstnodes SWE and SWG, and the voltage ripple causes some energy loss whenthe power on absorbing capacitors C43 and C44 is discharged to thestorage devices Cb11 and Cb10 through the discharging diodes D53 andD54. In the embodiment shown in FIG. 7F, the clamping circuit is the CDCclamping circuit (e.g., the CDC clamping shown in FIG. 7C), and the CDCclamping circuit is disposed between the first node and the groundterminal.

In the embodiment shown in FIG. 7F, N equals 2, and the power conversioncircuit is the same as that of FIG. 2B. The CDC clamping circuitscorresponding to the first and second switching power conversion unitsare substantially the same, thus the CDC clamping circuit correspondingto the first switching power conversion unit is taken as an example forexplanation. The CDC clamping circuit includes an absorbing circuit thatincludes an absorbing diode SD1′ and absorbing capacitors Cb1′ andCin1′. One terminal of the absorbing capacitor Cb1′ is seriallyconnected to the positive electrode of the absorbing diode SD1′, and oneterminal of the absorbing capacitor Cin1′ is serially connected to thenegative electrode of the absorbing diode SD1′. The absorbing circuit isconnected to the two ends of the third switch SR1 in parallel. Further,the components of the absorbing circuit are disposed near the thirdswitch SR1 on the layout of the printed circuit board, so as to achievethe shortest wiring path. In this embodiment, there is no need todispose the discharging circuit. By connecting the positive and negativeelectrodes of the absorbing diode SD1′ to the first node SWE of thefirst switching power conversion unit and the positive input port Vin+respectively, the energy absorption and long-distance discharge can berealized by the switches and capacitors of the power conversion circuit.

The work principle in this embodiment is similar to that of FIG. 7C. Atthe moment that the first switch S11 and the second switch S22 areturned on, the peak voltage generated on the two ends of the thirdswitch SR1 is absorbed by the absorbing capacitors Cb1′ and Cin1′ of thecorresponding CDC clamping circuit. Meanwhile, the absorbing capacitorsCb1′ and Cin1′ discharges to the storage device Cb10 and the inputcapacitor Cin. Consequently, the clamp protection for the third switchSR1 is realized. Similarly, the CDC clamping circuit corresponding tothe second switching power conversion unit utilizes the absorbingcapacitors Cb2′ and Cin2′ to absorb the peak voltage, and the absorbingcapacitors Cb2′ and Cin2′ discharges to the storage device Cb11 and theinput capacitor Cin. Consequently, the clamp protection for the thirdswitch SR2 is realized.

In this embodiment, the voltage drops on the absorbing capacitors Cin1′and Cin2′ are clamped to Vin, and the voltage drops on the absorbingcapacitors Cb1′ and Cb2′ are clamped to −Vin/2. Therefore, in thisembodiment, the voltage drops on the third switches SR1 and SR2 areclamped to substantially Vin/2, and it is allowed to employ the switchwith low withstanding-voltage level as the third switch. Moreover, inthis embodiment, there is no further special requirements to thecapacitances of the capacitors Cb1′, Cin1′, Cb2′ and Cin2′ except forabsorbing power, which makes the design simpler and reduces the loss.

In addition, all the diodes of the clamping circuits in aboveembodiments (e.g., the diodes D41, D51, D42 and D52 of FIG. 7A and FIG.7B, the diodes MD1′, D42 and D52 of FIG. 7C, the diodes D43 and D44 ofFIG. 7D and FIG. 7E, and the diodes SD1′ and SD2′ of FIG. 7E) can bereplaced by controllable switches.

In the first power conversion circuit of FIG. 2A, the sources of thesecond switches M21 and M22 are grounded, and the sources of the firstswitches M11 and M12 are connected to the capacitor Cb and the drain ofthe second switch M22 respectively. Therefore, the bootstrap supply isneeded for driving the first switches M11 and M12 in actualapplications. In addition, in the second power conversion circuit ofFIG. 2B, the sources of the third switches SR1 and SR2 are grounded, thesources of the second switches S21 and S22 are connected to the drainsof the third switches SR2 and SR1 respectively, and the sources of thefirst switches S11 and S12 are connected to the drains of the secondswitches S21 and S22 respectively. Therefore, the bootstrap supply isneeded for driving the first switches S11 and S12 and the secondswitches S21 and S22 in actual applications. In an embodiment, the powerconversion system further includes a bootstrap circuit and a pluralityof driving circuits, so as to control the first and second switches ofthe power conversion circuits and realize the bootstrap supply for thedriving to the switches.

FIG. 8A is a schematic circuit diagram illustrating a first powerconversion circuit, a bootstrap circuit and driving circuits accordingto a thirteenth embodiment of the present disclosure. FIG. 8B is aschematic circuit diagram illustrating a first power conversion circuit,a bootstrap circuit and driving circuits according to a fourteenthembodiment of the present disclosure. The bootstrap circuit and thedriving circuit of FIG. 8A and FIG. 8B can be applied to the first powerconversion circuit. As shown in FIG. 8A and FIG. 8B, the first powerconversion circuit further includes N nodes. The (n)th node Pn islocated between the first switch of the (n)th switching power conversionunit and the first switch of the (n+1)th switching power conversionunit. The (N)th node PN is located between the first and second switchesof the (N)th switching power conversion unit. The bootstrap circuitincludes N bootstrap capacitors and N bootstrap diodes. The N bootstrapdiodes are serially connected in sequence. One terminal (such as thenegative electrode) of the (n)th bootstrap capacitor is electricallyconnected to the (n)th node Pn, and the other terminal (such as thepositive electrode) of the (n)th bootstrap capacitor is electricallyconnected to the negative electrode of the (n)th bootstrap diode. Oneterminal (such as the negative electrode) of the (N)th bootstrapcapacitor is electrically connected to the (N)th node PN, and the otherterminal (such as the positive electrode) of the (N)th bootstrapcapacitor is electrically connected to the negative electrode of the(N)th bootstrap diode. The positive electrode of the (N)th bootstrapdiode receives the supply voltage Vcc. Each of the N driving circuits isconnected to the corresponding bootstrap capacitor. The driving of thefirst and second switches is powered by the positive electrode voltageof the bootstrap capacitor and the supply voltage Vcc. The drivingcircuits output the first and second driving signals for controlling thefirst and second switches of the corresponding power conversioncircuits. Consequently, through the bootstrap circuit and the drivingcircuit, the function of the bootstrap supply and the control ofswitches are realized, which enhances the applicability of the powerconversion circuit greatly and benefits the miniaturization of the powerconversion system product. Further, the structure of the bootstrapcircuit is simple so that the cost is low.

In an embodiment, the (n)th/(N)th driving circuit includes a first inputterminal, a second input terminal and a first output terminal. The firstinput terminal and the second input terminal of the (n)th drivingcircuit are electrically connected to the negative electrode of the(n)th bootstrap diode and the (n)th node respectively, and the firstoutput terminal of the (n)th driving circuit outputs the first drivingsignal for controlling the first switch of the (n)th switching powerconversion unit. Moreover, the high level and low level of the firstdriving signal outputted by the (n)th driving circuit equal the positiveelectrode voltage of the (n)th bootstrap capacitor and the voltage onthe (n)th node respectively. The first input terminal and the secondinput terminal of the (N)th driving circuit are electrically connectedto the negative electrode of the (N)th bootstrap diode and the (N)thnode respectively. The first output terminal of the (N)th drivingcircuit outputs the first driving signal for controlling the firstswitch of the (N)th switching power conversion unit. Moreover, the highlevel and low level of the first driving signal outputted by the (N)thdriving circuit equal the positive electrode voltage of the (N)thbootstrap capacitor and the voltage on the (N)th node respectively.

In an embodiment, the (n)th/(N)th driving circuit further includes athird input terminal, a fourth input terminal and a second outputterminal. The third input terminal and the fourth input terminal of the(n)th driving circuit are further electrically connected to the supplyvoltage and the ground terminal respectively, and the second outputterminal of the (n)th driving circuit further outputs the second drivingsignal for controlling the second switch of the (n)th switching powerconversion unit. Moreover, the high level and low level of the seconddriving signal equal the supply voltage and the voltage at the groundterminal respectively. The third input terminal and the fourth inputterminal of the (N)th driving circuit are further electrically connectedto the supply voltage and ground terminal respectively, and the secondoutput terminal of the (N)th driving circuit further outputs the seconddriving signal for controlling the second switch of the (N)th switchingpower conversion unit. Moreover, the high level and low level of thesecond driving signal equal the supply voltage and the voltage at theground terminal respectively.

In the embodiment shown in FIG. 8A, N equals 2. The supply voltage Vccis connected to one terminal (e.g., the positive electrode) of thesecond bootstrap capacitor C52 through the second bootstrap diode D62,and the other terminal (e.g., the negative electrode) of the bootstrapcapacitor C52 is connected to the second node P2. When the second switchM22 is turned on, the node P2 is shorted to the ground terminal, thebootstrap diode D62 is turned on, and the positive electrode voltageVcc1 of the bootstrap capacitor C52 is increased to Vcc (the voltagedrop caused by the conduction of diodes is omitted). When the secondswitch M22 is turned off, the node P2 is floated, the positive electrodevoltage Vcc1 of the bootstrap capacitor C52 is utilized to supply powerfor the driving circuit of the first switch M12 so as to increase thepotential of the driving of the first switch M12. The positive electrodevoltage Vcc1 of the bootstrap capacitor C52 is connected to one terminal(e.g., the positive electrode) of the first bootstrap capacitor C51through the first bootstrap diode D61, and the other terminal (e.g., thenegative electrode) of the bootstrap capacitor C51 is connected to thefirst node P1. When the first switch M12 is turned on, the node P1 isshorted to the node P2, the bootstrap diode D61 is turned on, and thepositive electrode voltage Vcc2 of the bootstrap capacitor C51 isincreased to Vcc1. When the first switch M12 is turned off, the positiveelectrode voltage Vcc2 of the bootstrap capacitor C51 is utilized tosupply power for the driving circuit of the first switch M11 so as toincrease the potential of the driving of the first switch M11.Therefore, each phase of the power conversion circuit can realize thebootstrap supply function by utilizing only one bootstrap diode and onebootstrap capacitor. The circuit structure is simple, and the cost islow, which enhances the applicability greatly and benefits theminiaturization of the power conversion system.

In addition, the driving circuit IC1 receives the control signal PWM1and is connected to the bootstrap capacitor C51 and the supply voltageVcc. The driving circuit IC1 outputs a first driving signal Dri-M11 anda second driving signal Dri-M21 according to the positive electrodevoltage Vcc2 of the bootstrap capacitor C51 and the supply voltage Vcc,so as to control the corresponding first and second switches M11 andM21. The driving circuit IC2 receives the control signal PWM2 and isconnected to the bootstrap capacitor C52 and the supply voltage Vcc. Thedriving circuit IC2 outputs a first driving signal Dri-M12 and a seconddriving signal Dri-M22 according to the positive electrode voltage Vcc1of the bootstrap capacitor C52 and the supply voltage Vcc, so as tocontrol the corresponding first and second switches M12 and M22.Moreover, the time sequences of the first driving signals Dri-M11 andDri-M12 are corresponding to the time sequences of the control signalsPWM1 and PWM2 respectively. The high and low levels of the first drivingsignal Dri-M11 equal the positive electrode voltage of the firstbootstrap capacitor C51 and the voltage on the first node P1respectively. The high and low levels of the first driving signalDri-M12 equal the positive electrode voltage of the second bootstrapcapacitor C52 and the voltage on the second node P2 respectively. In anembodiment, the driving circuit (IC1, IC2) is further connected to thecontroller 10 for receiving the control signal (PWM1, PWM2) andoutputting the driving signal accordingly. In this embodiment, the firstswitch M11 (the upper switch), the first switch M12 (the middle switch)and the second switch M22 (the lower switch) are connected in series.One terminal of the upper switch is electrically connected to thepositive input port, and one terminal of the lower switch iselectrically connected to the negative input port. The positiveelectrode voltage of the second bootstrap capacitor C52 is utilized tosupply power for the control signal of the middle switch. The positiveelectrode voltage of the first bootstrap capacitor C51 is utilized tosupply power for the control signal of the upper switch.

In the embodiment shown in FIG. 8B, N equals 3. The supply voltage Vccis connected to one terminal (e.g., the positive electrode) of the thirdbootstrap capacitor C53 through the third bootstrap diode D63, and theother terminal (e.g., the negative electrode) of the bootstrap capacitorC53 is connected to the third node P3. When the second switch M23 isturned on, the node P3 is shorted to the ground terminal, the bootstrapdiode D63 is turned on, and the positive electrode voltage Vcc1 of thebootstrap capacitor C53 is increased to Vcc. When the second switch M23is turned off, the node P3 is floated, the positive electrode voltageVcc1 of the bootstrap capacitor C53 is utilized to supply power for thedriving of the first switch M13 so as to increase the potential of thedriving of the first switch M13. The positive electrode voltage Vcc1 ofthe bootstrap capacitor C53 is connected to one terminal (e.g., thepositive electrode) of the second bootstrap capacitor C52 through thesecond bootstrap diode D62, and the other terminal (e.g., the negativeelectrode) of the bootstrap capacitor C52 is connected to the secondnode P2. When the first switch M13 is turned on, the node P2 is shortedto the node P3, the bootstrap diode D62 is turned on, and the positiveelectrode voltage Vcc2 of the bootstrap capacitor C52 is increased toVcc1. When the first switch M13 is turned off, the positive electrodevoltage Vcc2 of the bootstrap capacitor C52 is utilized to supply powerfor the driving circuit of the first switch M12 so as to increase thepotential of the driving of the first switch M12. The positive electrodevoltage Vcc2 of the bootstrap capacitor C52 is connected to one terminal(e.g., the positive electrode) of the first bootstrap capacitor C51through the first bootstrap diode D61, and the other terminal (e.g., thenegative electrode) of the bootstrap capacitor C51 is connected to thefirst node P1. When the first switch M12 is turned on, the node P1 isshorted to the node P2, the bootstrap diode D61 is turned on, and thepositive electrode voltage Vcc3 of the bootstrap capacitor C51 isincreased to Vcc2. When the first switch M12 is turned off, the positiveelectrode voltage Vcc3 of the bootstrap capacitor C51 is utilized tosupply power for the driving circuit of the first switch M11 so as toincrease the potential of the driving of the first switch M11.

In addition, the driving circuit IC1 receives the control signal PWM1and is connected to the bootstrap capacitor C51 and the supply voltageVcc. The driving circuit IC1 outputs a first driving signal Dri-M11 anda second driving signal Dri-M21 according to the positive electrodevoltage Vcc3 of the bootstrap capacitor C51 and the supply voltage Vcc,so as to control the corresponding first and second switches M11 andM21. The driving circuit IC2 receives the control signal PWM2 and isconnected to the bootstrap capacitor C52 and the supply voltage Vcc. Thedriving circuit IC2 outputs a first driving signal Dri-M12 and a seconddriving signal Dri-M22 according to the positive electrode voltage Vcc2of the bootstrap capacitor C52 and the supply voltage Vcc, so as tocontrol the corresponding first and second switches M12 and M22. Thedriving circuit IC3 receives the control signal PWM1 and is connected tothe bootstrap capacitor C53 and the supply voltage Vcc. The drivingcircuit IC3 outputs a first driving signal Dri-M13 and a second drivingsignal Dri-M23 according to the positive electrode voltage Vcc1 of thebootstrap capacitor C53 and the supply voltage Vcc, so as to control thecorresponding first and second switches M13 and M23.

Moreover, the time sequences of the first driving signals Dri-M11 andDri-M13 are corresponding to the time sequence of the control signalPWM1, and the time sequence of the first driving signal Dri-M12 iscorresponding to the time sequence of the control signal PWM2. The highand low levels of the first driving signal Dri-M11 equal the positiveelectrode voltage of the first bootstrap capacitor C51 and the voltageon the first node P1 respectively. The high and low levels of the firstdriving signal Dri-M12 equal the positive electrode voltage of thesecond bootstrap capacitor C52 and the voltage on the second node P2respectively. The high and low levels of the first driving signalDri-M13 equal the positive electrode voltage of the third bootstrapcapacitor C53 and the voltage on the third node P3 respectively. In anembodiment, the driving circuit (IC1, IC2, IC3) is further connected tothe controller 10 for receiving the control signal (PWM1, PWM2) andoutputting the driving signal accordingly.

FIG. 8C is a schematic circuit diagram illustrating a second powerconversion circuit, bootstrap circuits and driving circuits according tothe fifteenth embodiment of the present disclosure. The bootstrapcircuit and driving circuit of FIG. 8C can be applied to the secondpower conversion circuit. As shown in FIG. 8C, the second powerconversion circuit includes N bridge arms, and each of the N bridge armsincludes a first switch, a second switch and a third switch connected inseries, where N is an integer larger than or equal to 2. Each bridge armincludes two nodes which are a first node and a second node. The firstnode is located between the first and second switches of the bridge arm,and the second node is located between the second and third switches ofthe bridge arm. Taking the first bridge arm as an example, the firstbridge arm is formed by a first switch S11, a second switch S21 and athird switch SR2 serially connected, the first node SWE is locatedbetween the first and second switches S11 and S21, and the second nodeSWH is located between the second and third switches S21 and SR2. Eachbridge arm is corresponding to one bootstrap circuit. Each bootstrapcircuit includes two bootstrap capacitors and two bootstrap diodes, andthe two bootstrap diodes are serially connected in series. The negativeelectrode of the first bootstrap capacitor is electrically connected tothe first node of the corresponding bridge arm. The positive electrodeof the first bootstrap capacitor is electrically connected to thenegative electrode of the first bootstrap diode. The positive electrodeof the first bootstrap diode is electrically connected to the positiveelectrode of the second bootstrap capacitor. The negative electrode ofthe second bootstrap capacitor is electrically connected to the secondnode of the corresponding bridge arm. The positive electrode of thesecond bootstrap capacitor is electrically connected to the negativeelectrode of the second bootstrap diode. The positive electrode of thesecond bootstrap diode receives the supply voltage Vcc.

Please refer to FIG. 8C again. Each bridge arm is corresponding to twodriving circuits, and each driving circuit is connected to thecorresponding bootstrap capacitor. The driving of the first, second andthird switches is powered by the positive electrode voltage of thebootstrap capacitor and the supply voltage Vcc. The driving circuitsoutput the first, second and third driving signals for controlling thefirst, second and third switches of the corresponding bridge arm.Consequently, through the bootstrap circuit and the driving circuit, thebootstrap supply function and the control of switches are realized,which enhances the applicability of the power conversion circuit greatlyand benefits the miniaturization of the power conversion system product.Further, the structure of the bootstrap circuit is simple so that thecost is low.

In an embodiment, with regard to each bridge arm, the input terminals ofthe corresponding first driving circuit are electrically connected tothe negative electrode of the first bootstrap diode and the first noderespectively. The output terminal of the corresponding first drivingcircuit outputs a first driving signal for controlling the correspondingfirst switch. The high and low levels of the first driving signaloutputted by the first driving circuit equal the positive electrodevoltage of the first bootstrap capacitor and the voltage on the firstnode. The input terminals of the corresponding second driving circuitare electrically connected to the negative electrode of the secondbootstrap diode and the second node respectively. The output terminal ofthe corresponding second driving circuit outputs a second driving signaland a third driving signal for controlling the corresponding second andthird switches. The high and low levels of the second driving signaloutputted by the second driving circuit equal the positive electrodevoltage of the second bootstrap capacitor and the voltage on the secondnode.

In the embodiment shown in FIG. 8C, N equals 2. The second powerconversion circuit includes two bridge arms, and the second powerconversion system includes two bootstrap circuits and four drivingcircuits. The first bridge arm and the corresponding one bootstrapcircuit and two driving circuits are taken as an example. The supplyvoltage Vcc is connected to the positive electrode of the secondbootstrap capacitor C14 through the second bootstrap diode D11, and thenegative electrode of the bootstrap capacitor C14 is connected to thesecond node SWH. When the third switch SR2 is turned on, the second nodeSWH is shorted to the ground terminal, the bootstrap diode D11 is turnedon, and the positive electrode voltage Vcc11 of the bootstrap capacitorC14 is increased to Vcc (the voltage drop caused by the conduction ofdiodes is omitted). When the third switch SR2 is turned off, the secondnode SWH is floated, the positive electrode voltage Vcc11 of thebootstrap capacitor C14 is utilized to supply power for the drivingcircuit of the second switch S21 so as to increase the potential of thedriving of the second switch S21. The positive electrode voltage Vcc11of the bootstrap capacitor C14 is connected to the positive electrode ofthe first bootstrap capacitor C15 through the first bootstrap diode D12,and the negative electrode of the bootstrap capacitor C15 is connectedto the first node SWE. When the second switch S21 is turned on, thefirst node SWE is shorted to the second node SWH, the bootstrap diodeD12 is turned on, and the positive electrode voltage Vcc12 of thebootstrap capacitor C15 is increased to Vcc11. When the second switchS21 is turned off, the positive electrode voltage Vcc12 of the bootstrapcapacitor C15 is utilized to supply power for the driving of the firstswitch S11 so as to increase the potential of the driving of the firstswitch S11. Therefore, each bridge arm can realize the bootstrap supplyfunction by utilizing two bootstrap diodes and two bootstrap capacitors.The circuit structure is simple, and the cost is low, which enhances theapplicability greatly and benefits the miniaturization of the powerconversion system.

In this embodiment, the first switch S11 (the upper switch), the secondswitch S21 (the middle switch) and the third switch SR2 (the lowerswitch) of one bridge arm are connected in series. One terminal of theupper switch is electrically connected to the positive input port, andone terminal of the lower switch is electrically connected to thenegative input port. The positive electrode voltage of the secondbootstrap capacitor C14 is utilized to supply power for the controlsignal of the middle switch, and the positive electrode voltage of thefirst bootstrap capacitor C15 is utilized to supply power for thecontrol signal of the upper switch. Similarly, the first switch S12 (theupper switch), the second switch S22 (the middle switch) and the thirdswitch SR1 (the lower switch) of the other bridge arm are connected inseries. One terminal of the upper switch is electrically connected tothe positive input port, and one terminal of the lower switch iselectrically connected to the negative input port. The positiveelectrode voltage of the second bootstrap capacitor C24 is utilized tosupply power for the control signal of the middle switch, and thepositive electrode voltage of the first bootstrap capacitor C25 isutilized to supply power for the control signal of the upper switch.

In addition, the driving circuit IC11 receives the control signal PWM1and is connected to the bootstrap capacitor C15 and the supply voltageVcc. The driving circuit IC11 outputs a first driving signal Dri-S11according to the positive electrode voltage Vcc12 of the bootstrapcapacitor C15 and the supply voltage Vcc, so as to control thecorresponding first switch S11. The driving circuit IC12 receives thecontrol signal PWM2 and is connected to the bootstrap capacitor C14 andthe supply voltage Vcc. The driving circuit IC12 outputs a seconddriving signal Dri-S21 and a third driving signal Dri-SR2 according tothe positive electrode voltage Vcc11 of the bootstrap capacitor C14 andthe supply voltage Vcc, so as to control the corresponding second andthird switches S21 and SR2. Moreover, the time sequences of the firstdriving signals Dri-S11 and Dri-S21 are corresponding to the timesequences of the control signals PWM1 and PWM2 respectively. The thirddriving signal Dri-SR2 is complementary to the control signal PWM2. Thehigh and low levels of the first driving signal Dri-S11 equal thepositive electrode voltage of the first bootstrap capacitor C15 and thevoltage on the first node SWE respectively. The high and low levels ofthe second driving signal Dri-S21 equal the positive electrode voltageof the second bootstrap capacitor C14 and the voltage on the second nodeSWH respectively.

In an embodiment, the driving circuit (IC11, IC12) is further connectedto the controller 10 for receiving the control signal (PWM1, PWM2) andoutputting the driving signal accordingly. The work principle of thebootstrap circuit and the driving circuit corresponding to the secondbridge arm is similar to that corresponding to the first bridge arm,thus the detailed description thereof is omitted herein. When the powerconversion circuit includes N bridge arms, the bootstrap supply andgeneration of driving signal can be achieved in the same manner. Inaddition, the manner of bootstrap supply and driving is not limited tobe applied to the circuit topologies shown in FIG. 8A, FIG. 8B and FIG.8C. The bootstrap circuit and the driving circuit of the presentdisclosure can be applied to any circuit topology including threeswitches serially connected and satisfying the following conditions. Thethree switches are an upper switch, a middle switch and a lower switchrespectively and are electrically connected to the input port of thepower conversion circuit. The lower and middle switches are not in theconducting state at the same time, and the middle and upper switches arenot in the conducting state at the same time.

In the above embodiments, the said switches may be MOS, SiC or GaN.Further, the lower switch can be replaced by the free-wheeling diode,and the positive electrode of the free-wheeling diode is electricallyconnected to the negative output port. For example, the second switchesM21 and M22 of FIG. 2A, FIG. 4A, FIG. 5A, FIG. 7A, FIG. 7B and FIG. 8Acan be replaced by the free-wheeling diodes, and the second switchesM21, M22 and M23 of FIG. 6A and FIG. 8A can be replaced by thefree-wheeling diodes. In another embodiment, all the diodes of thebootstrap circuits can be replaced by the controllable switches. Forexample, the diodes D61 and D62 of FIG. 8A and diodes D61, D62 and D63of FIG. 8B can be replaced by the controllable switches. The firstterminal of the controllable switch is corresponding to positiveelectrode of the bootstrap diode, and the second terminal of thecontrollable switch is corresponding to the negative electrode of thebootstrap diode. The controllable switch may be MOS, SiC or GaN.

In addition, the switching power conversion unit of the power conversioncircuit includes inductors. In order to realize the miniaturization ofthe power conversion system product, the magnetic core assembly aroundwhich the inductor is wound may be designed to make the substrate widthof the magnetic core assembly as small as possible for reducing theheight of the power conversion system product. In the case that N equals2, the actual implementation of the magnetic core assembly isexemplified as follows.

FIG. 9A is a schematic perspective view illustrating a part of themagnetic core assembly according to an embodiment of the presentdisclosure. FIG. 9B schematically shows the direction of AC magneticflux in the magnetic core assembly of FIG. 9A. FIG. 9C is a schematicoscillogram showing the AC magnetic flux in the magnetic core assemblyof FIG. 9A in one switching period. Please refer to FIG. 9A in view ofFIG. 2A and FIG. 2B. The two inductors L1 and L2 of the two switchingpower conversion units are wound around the same magnetic core assembly.The magnetic core assembly includes two substrates, two winding pillarsand two side pillars. The two winding pillars and the two side pillarsare disposed on at least one of the two substrates and are locatedbetween the two substrates. The magnetic core assembly is formed by anupper magnetic core and a lower magnetic core assembled to each other.The lower magnetic core 4 is taken as an example for explaining themagnetic core structure and the winding direction. The lower magneticcore 4 includes two winding pillars 41 and 42, two side pillars 43 and44 and a substrate 45. The winding pillars 41 and 42 and the sidepillars 43 and 44 are disposed on the substrate 45. The two side pillars43 and 44 are disposed at the two opposite sides of the winding pillars41 and 42 respectively. From the viewpoint of looking squarely at FIG.9A, the winding pillar 41 is disposed in front of the winding pillar 42,and the two side pillars 43 and 44 are disposed at the left and rightsides of the winding pillars 41 and 42 respectively. In an embodiment,the distance between the centers of the winding pillars 41 and 42, thevertical distance from the center of the winding pillar 41 to the sidepillar 43, and the vertical distance from the center of the windingpillar 41 to the side pillar 44 are all the same. In an embodiment, onlythe side pillars 43 and 44 have air gap, and the length of the two airgaps are substantially the same. Alternatively, each of the two sidepillars 43 and 44 and the two winding pillars 41 and 42 has an air gap.The length of the air gaps on the two side pillars are substantially thesame, the length of the air gaps on the two winding pillars aresubstantially the same, and the length of the air gap on the side pillaris larger than or equal to the length of the air gap on the windingpillar.

For example, the winding of two inductors L1 and L2 of FIG. 2A are woundaround the two winding pillars 41 and 42, and the direction of DCcurrent is shown as FIG. 9A. The directions of DC magnetic flux on thewinding pillars 41 and 42 are the same. As shown in FIG. 9C, the dutyratio D of the switches M11 and M12 is 25%, and the control signals ofthe two switches M11 and M12 are 180 degrees out of phase with respectto each other. The interval from the time t0 to the time t4 is aswitching period Ts. During the interval from the time t0 to the timet1, the first switch M11 is turned on, and the AC magnetic flux Φac1flowing through the winding pillar 41 is increased linearly. The ACmagnetic flux Φac1 equals 3Φ at the time t1. The direction of the ACmagnetic flux Φac2 flowing through the winding pillar 42 is opposite tothe direction of the AC magnetic flux tact. The AC magnetic flux Φac2equals −Φ at the time t1. Consequently, one third of the AC magneticflux flowing through the winding pillar 41 flows to the winding pillar42. Moreover, as shown in FIG. 9B, the winding pillar 41 is located atthe central position between the two side pillars 43 and 44, namely thevertical distance from the center of the winding pillar 41 to the sidepillar 43 equals that between the center of the winding pillar 41 andthe side pillar 44. Accordingly, the parts of the AC magnetic flux Φac1flowing to the winding pillar 42, the side pillar 43 and the side pillar44 respectively are all the same. It is noted that the AC magnetic fluxΦac1 flowing through the winding pillar 41 flows to the winding pillar42 and the two side pillars 43 and 44 at the time t1. Similarly, the ACmagnetic flux at the time t0, t2, t3 and t4 can be derived, and thedetailed description thereof is omitted herein. The above magnetic fluxvariation Φ is used for illustration and does not mean specificnumerical value. Since the AC magnetic flux Φac1 flowing through thewinding pillar 41 is divided into three parts that flows to the sidepillars 43 and 44 and the winding pillar 42 respectively, the ACmagnetic flux is substantially shared equally. Therefore, the thicknessof the substrate 45 is reduced, and the height of the power conversionsystem product is reduced, which makes the power conversion systemproduct become thinner and increases the applicability. Furthermore, inthe power conversion system, the power density is improved, and thevertical thermal resistance is reduced. It is noted that the duty ratioD is not limited to 25% in this actual implementation of magnetic coreassembly, the duty ratio is allowed to be larger than or equal to 15%and smaller than or equal to 35%. The effect of sharing the AC magneticflux is the best when the duty ratio D is 25%. In addition, the uppermagnetic core of the magnetic core assembly may have the same structurewith the lower magnetic core 4, or the upper magnetic core may be anI-type magnetic core. The winding direction of the inductors L1 and L2are not limited to that shown in the figures. If the AC magnetic flux isensured to be divided for reducing the thickness of substrate, thewinding direction can be varied freely.

FIG. 9D is a schematic perspective view illustrating a part of themagnetic core assembly according to another embodiment of the presentdisclosure. FIG. 9E schematically shows the direction of AC magneticflux in the magnetic core assembly of FIG. 9D. FIG. 9F is a schematicperspective view illustrating a part of the magnetic core assemblyaccording to further another embodiment of the present disclosure.Please refer to FIG. 9A in view of FIG. 2A and FIG. 2B. The twoinductors L1 and L2 of the two switching power conversion units arewound around the same magnetic core assembly. The magnetic core assemblyincludes two substrates, two winding pillars and one side pillar. Thetwo winding pillars and the side pillar are disposed on at least one ofthe two substrates and are located between the two substrates. Themagnetic core assembly is formed by an upper magnetic core and a lowermagnetic core assembled to each other. The lower magnetic core 4 istaken as an example for explaining the magnetic core structure and thewinding direction. The lower magnetic core 4 includes two windingpillars 41 and 42, one side pillar 43 and a substrate 45. The windingpillars 41 and 42 and the side pillar 43 are disposed on the substrate45. From the viewpoint of looking squarely at FIG. 9D, the windingpillar 41 is disposed in front of the winding pillar 42, and the sidepillar 43 is disposed at one side of the winding pillars 41 and 42. Inan embodiment, the distance between the centers of the winding pillars41 and 42 and the vertical distance from the centers of the windingpillar 41 to the side pillar 43 are the same. In an embodiment, only theside pillar 43 has an air gap. Alternatively, each of the side pillar 43and the two winding pillars 41 and 42 has an air gap. The length of theair gaps on the two winding pillars are substantially the same, and thelength of the air gap on the side pillar is larger than or equal to thelength of the air gap on the winding pillar.

For example, the winding of two inductors L1 and L2 are wound around thetwo winding pillars 41 and 42, and the direction of DC current is shownas FIG. 9D. The direction of DC magnetic flux on the winding pillars 41and 42 are the same. As shown in FIG. 9D and FIG. 9E, one third of theAC magnetic flux Φac1 flowing through the winding pillar 41 flows to thewinding pillar 42, and two thirds of the AC magnetic flux Φac1 flows tothe side pillar 43. Even though the AC magnetic flux Φac1 flowingthrough the winding pillar 41 cannot be divided equally into two partsflowing toward the side pillar 43 and the winding pillar 42respectively, the thickness of the substrate 45 can still be reduced tosome extent. Consequently, the height of the power conversion systemproduct is reduced. Other details of this embodiment can be derivedaccording to the embodiment shown in FIG. 0.9A and is omitted herein.

In another embodiment, as shown in FIG. 9F, the side pillar 43 of FIG.9D can be divided into two side pillars 43 a and 43 b. The two sidepillars 43 a and 43 b are disposed at the same side of the two windingpillars 41 and 42. The AC magnetic flux flowing through the windingpillar 41 flows to the side pillars 43 b and the winding pillar 42.Similarly, the AC magnetic flux flowing through the winding pillar 42flows to the side pillar 43 a and the winding pillar 41. Other detailsof this embodiment can be derived according to the embodiment shown inFIG. 9D and is omitted herein.

FIG. 10A is a schematic perspective view illustrating a part of themagnetic core assembly according to another embodiment of the presentdisclosure. FIG. 10B schematically shows the direction of AC magneticflux in the magnetic core assembly of FIG. 10A. FIG. 10C is a schematicoscillogram showing the AC magnetic flux in the magnetic core assemblyof FIG. 10A in one switching period. Please refer to FIG. 10A in view ofFIG. 2A and FIG. 2B. The two inductors L1 and L2 of the two switchingpower conversion units are wound around the same magnetic core assembly.The magnetic core assembly includes two substrates, four winding pillarsand an auxiliary pillar unit. The four winding pillars and the auxiliarypillar unit are disposed on at least one of the two substrates and arelocated between the two substrates. The winding of the inductor L1 iswound around at least two winding pillars, and the winding of theinductor L2 is wound around at least two winding pillars. The connectingline of the centers of the four winding pillars forms a quadrangle. Inthis embodiment, the auxiliary pillar unit includes two middle pillars(i.e., the auxiliary pillars). The magnetic core assembly is formed byan upper magnetic core and a lower magnetic core assembled to eachother. The lower magnetic core 5 is taken as an example for explainingthe magnetic core structure and the winding direction. The lowermagnetic core 5 includes a first winding pillar 51, a second windingpillar 52, a third winding pillar 53, a fourth winding pillar 54, afirst middle pillar 55, a second middle pillar 56 and a substrate 57.The first winding pillar 51, the second winding pillar 52, the thirdwinding pillar 53, the fourth winding pillar 54, the first middle pillar55 and the second middle pillar 56 are disposed on the substrate 57. Thefirst middle pillar 55 is located between the first winding pillar 51and the fourth winding pillar 54, and the second middle pillar 56 islocated between the second winding pillar 52 and the third windingpillar 53. The connecting line of the centers of the first, second,third and fourth winding pillars 51, 52, 53 and 54 forms a quadrangle.The first and third winding pillars 51 and 53 are located on a firstdiagonal line of the quadrangle, and the second and fourth windingpillars 52 and 54 are located on a second diagonal line of thequadrangle.

For example, the winding of the inductor L1 is wound around the firstand third winding pillars 51 and 53, and the winding of the inductor L2is wound around the second and fourth winding pillar 52 and 54. Thedirection of DC current is shown as FIG. 10A, and the DC magnetic fluxflowing through the fourth winding pillars (51, 52, 53, 54) aresuperimposed on the two middle pillars (55, 56). As shown in FIG. 10Band FIG. 10C, the duty ratio D is 50%, and the interval from the time t0to the time t2 is a switching period Ts. During the interval from thetime t0 to the time t1, the first switch M11 is turned on, the ACmagnetic flux Φac3 flowing through the first and third winding pillars51 and 53 are increased linearly, and the AC magnetic flux Φac4 flowingthrough the second and fourth winding pillars 52 and 54 are decreasedlinearly. At the time t1, one half of the AC magnetic flux flowingthrough the first winding pillar 51 flows to the second winding pillar52, and the other half of the AC magnetic flux flowing through the firstwinding pillar 51 flows to the fourth winding pillar 54. One half of theAC magnetic flux flowing through the third winding pillar 53 flows tothe second winding pillar 52, and the other half of the AC magnetic fluxflowing through the third winding pillar 53 flows to the fourth windingpillar 54. During the interval from the time t1 to the time t2, the ACmagnetic flux Φac4 flowing through the second and fourth winding pillars52 and 54 are increased linearly, and the AC magnetic flux Φac3 flowingthrough the first and third winding pillars 51 and 53 are decreasedlinearly. At the time t2, one half of the AC magnetic flux flowingthrough the second winding pillar 52 flows to the first winding pillar51, and the other half of the AC magnetic flux flowing through thesecond winding pillar 52 flows to the third winding pillar 53. One halfof the AC magnetic flux flowing through the fourth winding pillar 54flows to the first winding pillar 51, and the other half of the ACmagnetic flux flowing through the fourth winding pillar 54 flows to thethird winding pillar 53.

Since the AC magnetic flux flowing through the winding pillar is dividedinto two parts that flows to the two neighboring winding pillarsrespectively, the AC magnetic flux is substantially divided equally.Therefore, the thickness of the substrate 57 is reduced, and the heightof the power conversion system product is reduced, which makes the powerconversion system product become thinner and increases theapplicability. Furthermore, in the power conversion system, the powerdensity is improved, and the vertical thermal resistance is reduced. Itis noted that the duty ratio D is not limited to 50% in this actualimplementation of magnetic core assembly, the duty ratio is allowed tobe larger than or equal to 30% and smaller than or equal to 70%. The ACmagnetic flux flowing out of the winding pillar flows to the twoneighboring winding pillars and one neighboring middle pillar, and threeclosed magnetic flux loops are formed accordingly. The effect of sharingthe AC magnetic flux is the best when the duty ratio D is 50%. Inaddition, the upper magnetic core of the magnetic core assembly may havethe same structure with the lower magnetic core 5, or the upper magneticcore may be an I-type magnetic core. The winding direction of theinductors L1 and L2 are not limited to that shown in the figures. If theAC magnetic flux is ensured to be divided for reducing the thickness ofsubstrate, the winding direction can be varied freely.

In another embodiment with the duty ratio D equal to 50%, as shown inFIG. 10D, the two middle pillars of FIG. 10A are combined into onemiddle pillar 65, and the cross section of the middle pillar 65 is arectangle. The winding pillars 61, 62, 63 and 64 are corresponding tothe winding pillars 51, 52, 53 and 54 of FIG. 10A respectively. Themiddle pillar 65 is located at the center of the set of the windingpillars 61 and 62 and the set of the winding pillars 63 and 64. In anembodiment, the winding direction is shown as FIG. 10E, and FIG. 10E isa vertical view of the FIG. 10D. One winding is wound around the windingpillars 62 and 64 and the middle pillar 65 anti-clockwisely and formsone inductor with the winding pillars 62 and 64. The other winding iswound around the winding pillars 61 and 63 and the middle pillar 65anti-clockwisely and forms the other inductor with the winding pillars61 and 63. In another embodiment, the winding direction is shown as FIG.10F, and FIG. 10F is a vertical view of the FIG. 10D. One winding isfirst wound around the winding pillar 61 anti-clockwisely, then woundthrough the outer edge side of the winding pillar 64, and finally woundaround the winding pillar 63 anti-clockwisely. Therefore, this windingand the winding pillars 61 and 63 form one inductor. The other windingis first wound around the winding pillar 62 anti-clockwisely, then woundthrough the outer edge side of the winding pillar 61, and finally woundaround the winding pillar 64 anti-clockwisely. Therefore, this windingand the winding pillars 62 and 64 form the other inductor. In addition,in an embodiment, the middle pillar 65 which has a cross section in theshape of a rectangle may be replaced by a middle pillar 75 which has across section in the shape of a square, as shown in FIG. 10G.Alternatively, the middle pillar 65 may be replaced by a middle pillar85 which has a cross section in the shape of a circle or an oval, asshown in FIG. 10H. The winding direction in the embodiments shown inFIGS. 10G and 10H can be derived according to that shown in FIG. 10E andFIG. 10F. Moreover, in those embodiments, the directions of DC magneticflux on the winding pillars are the same. When the duty ratio D is 50%,the AC magnetic flux flowing through any winding pillar is dividedequally into two parts flowing toward the two neighboring windingpillars (see FIG. 10B). Consequently, the AC magnetic flux is sharedequally, and thus the thickness of the magnetic core substrate isreduced.

In another embodiment with the duty ratio D equal to 50%, the magneticcore assembly may be constructed by the magnetic core structure shown inFIG. 10I. The lower magnetic core includes four winding pillars 91, 92,93 and 94, an auxiliary pillar unit and a substrate 97. The auxiliarypillar unit includes two side pillars 95 and 96. A quadrangle is formedby the connecting line of the centers of the four winding pillars, andthe sides pillars are located at the two sides of the quadranglerespectively. In this embodiment, the winding direction may be similarto that shown in FIG. 10A, so as to make the DC magnetic flux on thewinding pillars having the same direction. When the duty ratio D is 50%,the AC magnetic flux flowing through any winding pillar is dividedequally into two parts flowing toward the two neighboring windingpillars (see FIG. 10B). Consequently, the AC magnetic flux is sharedequally, and thus the thickness of the magnetic core substrate isreduced. In another embodiment, the side pillar 95 may be located at aside of the connecting line of the winding pillars 91 and 94, and theside pillar 96 may be located at a side of the connecting lone of thewinding pillars 92 and 93 correspondingly.

In the embodiments shown in FIG. 10D, FIG. 10G, FIG. 10H and FIG. 10I,the manner of dividing the AC magnetic flux is not limited to be appliedto the situation that the duty ratio is 50%. When the duty ratio D islarger than or equal to 30% and is smaller than or equal to 70%, the ACmagnetic flux flowing out of the winding pillar can flow toward the twoneighboring winding pillars and the neighboring middle or side pillarand form closed magnetic flux loop. The effect of sharing the ACmagnetic flux is the best when the duty ratio D is 50%. When the ACmagnetic flux is not shared equally, a part of the AC magnetic fluxflows through the auxiliary pillar. Under this circumstance, an air gapis disposed on the auxiliary pillar unit. If the auxiliary pillar unitincludes two auxiliary pillars, the length of the air gaps on the twoauxiliary pillars are substantially the same. Alternatively, each of theauxiliary pillar unit and the four winding pillars has an air gap. Thelength of the air gaps on the auxiliary pillar unit are substantiallythe same, and the length of the air gaps on the four winding pillars aresubstantially the same. The length of the air gap on the auxiliarypillar is larger than or equal to the length of the air gap on thewinding pillar. In addition, the upper magnetic core may have the samestructure with the lower magnetic core, or the upper magnetic core maybe an I-type magnetic core. The winding direction of the inductor is notlimited. If the AC magnetic flux is ensured to be divided for reducingthe thickness of substrate, the winding direction can be varied freely.Further, the structure of the magnetic core assembly is exemplified inthe figures, but the exact positions of the pillars are not limitedthereto. For example, when the winding pillar, the side pillar or theauxiliary is disposed at a side of the substrate, the pillar may beclose to the edge of the substrate, or there may be a distance betweenthe pillar and the edge of the substrate.

In above embodiments, the spatially relative terms, such as “on,”“below,” “lower,” “above,” “upper” and the like, may be used herein forease of description to describe one element or feature's relationship toanother element(s) or feature(s) as illustrated in the figures. Thespatially relative terms are intended to encompass differentorientations of the device in use or operation in addition to theorientation depicted in the figures. The apparatus may be otherwiseoriented (rotated 90 degrees or at other orientations) and the spatiallyrelative descriptors used herein may likewise be interpretedaccordingly.

With regard to the power conversion circuit shown in FIG. 2A and FIG.2B, the frequency of the circuit ripple at the input side thereof is aswitching frequency fs. Even though the two switching power conversionunits are connected in series, the ripple frequency is not increased forreducing the ripple amplitude. Accordingly, there is a need of providinga filter component with large volume at the input port to filter thecurrent ripple. However, the filter component with large volume wouldincrease the volume of the power conversion system.

For the high power applications, in an embodiment, the presentdisclosure utilizes a plurality of power conversion circuits connectedin parallel and interleaved with each other to enlarge the load capacityof the power conversion system. The power conversion system includes Xpower conversion circuits, where X is an integer larger than 1. The Xpower conversion circuits are designated as A1, A2 . . . AX in FIG. 11Aand FIG. 11B, and the X power conversion circuits are designated as B1,B2 . . . BX in FIG. 11C. The input ports of the X power conversioncircuits are connected in parallel, and the output ports of the X powerconversion circuits are connected in parallel. The circuit structure ofeach power conversion circuit is similar to that described above, andthe detailed description thereof is omitted herein. In addition, thepower conversion system further includes a controller 100.

FIG. 11A and FIG. 11B show the embodiments that a plurality of firstpower conversion circuits are connected in parallel and interleaved witheach other. In the embodiment shown in FIG. 11A, X is odd, and thecontroller 100 outputs X sets of control signals (PWM11, PWM12), (PWM21,PWM22) . . . (PWMX1, PWMX2). The control signals PWM11, PWM21 . . .PWMX1 are 360/X out of phase with respect to each other in sequence. Thecontrol signals PWM11 and PWM12 are utilized to control the powerconversion circuit A1, the control signals PWM21 and PWM22 are utilizedto control the power conversion circuit A2, and so forth, and thecontrol signals PWMX1 and PWMX2 are utilized to control the powerconversion circuit AX. The detailed control manner similar to that shownin FIG. 2A, FIG. 3A and FIG. 3B, and is omitted herein. In theembodiment shown in FIG. 11B, X is even, and the controller 100 outputsY sets of control signals (PWM11, PWM12), (PWM21, PWM22) . . . (PWMY1,PWMY2), where Y equals X/2. The control signals PWM11, PWM21 . . . PWMY1are 360/Y (i.e., 720/X) out of phase with respect to each other insequence. The control signals PWM11 and PWM12 are utilized to controlthe power conversion circuits A1 and A(Y+1), the control signals PWM21and PWM22 are utilized to control the power conversion circuits A2 andA(Y+2), and so forth, and the control signals PWMY1 and PWMY2 areutilized to control the power conversion circuits AY and AX. FIG. 11Cshows the embodiments that a plurality of second power conversioncircuits are connected in parallel and interleaved with each other. Inthe embodiment shown in FIG. 11C, the controller 100 outputs X sets ofcontrol signals (PWM11, PWM12), (PWM21, PWM22) . . . (PWMX1, PWMX2). Thecontrol signals PWM11, PWM21 . . . PWMX1 are 360/2X out of phase withrespect to each other in sequence. The control signals PWM11 and PWM12are utilized to control the power conversion circuit B1, the controlsignals PWM21 and PWM22 are utilized to control the power conversioncircuit B2, and so forth, and the control signals PWMX1 and PWMX2 areutilized to control the power conversion circuit BX. Through the phasedifference among the control signals, the X power conversion circuitscan be connected in parallel and interleaved with each other.Consequently, the current ripple at the input side of the powerconversion system is reduced, and it is allowed to employ the filtercomponent with small volume so that the size of the power conversionsystem is reduced.

Taking the power conversion system including two first power conversioncircuits as an example (i.e., X equals 2), the two first powerconversion circuits are connected in parallel and interleaved with eachother. As shown in FIG. 12, for the two first power conversion circuitsA1 and A2, the input ports are connected in parallel, and the outputports are connected in parallel. Each of the input ports may have atleast one input capacitor Cin (see FIG. 12), or the input ports mayshare one set of input capacitor. Each of the output ports may have atleast one output capacitor, or the output ports may share one set ofoutput capacitor Co (see FIG. 12). The power conversion system furtherincludes a controller 100, and the controller 100 outputs a set of PWMcontrol signals PWM11 and PWM12. In the first power conversion circuitA1, the two ends of the storage device Cba have a first node SWAa and asecond node SWBa respectively. The first switch M11 a of the firstswitching power conversion unit is controlled by the control signalPWM11, and the control signal of the second switch M21 a of the firstswitching power conversion unit is complementary to the control signalPWM11. The first switch M12 a of the second switching power conversionunit is controlled by the control signal PWM12, and the control signalof the second switch M22 a of the second switching power conversion unitis complementary to the control signal PWM12. In the second powerconversion circuit A2, the two ends of the storage device Cbb have afirst node SWAb and a second node SWBb respectively. The first switchM11 b of the first switching power conversion unit is controlled by thecontrol signal PWM12, and the control signal of the second switch M21 bof the first switching power conversion unit is complementary to thecontrol signal PWM12. The first switch M12 b of the second switchingpower conversion unit is controlled by the control signal PWM11, and thecontrol signal of the second switch M22 b of the second switching powerconversion unit is complementary to the control signal PWM11.

With regard to the two power conversion circuits A1 and A2 connected inparallel and interleaved with each other of FIG. 12, the correspondingprecharge circuit may be the circuits shown as FIG. 13A. As shown inFIG. 13A, two identical precharge circuits are utilized to realize theprecharge for the two storage devices Cba and Cbb, the precharge circuitis similar to that shown in FIG. 5A and FIG. 5B, and the detaileddescription thereof is omitted herein. For example, the power circuit isa flyback circuit. The winding T3 a of the precharge circuit ispositively coupled to the magnetic element T1, and the turns ratio ofthe winding T3 a to the magnetic element T1 is 1:2. The output of theprecharge circuit is electrically connected to the first node SWAa andthe second node SWBa so as to precharge the storage device Cba. Thewinding T3 b of the precharge circuit is positively coupled to themagnetic element T1, and the turns ratio of the winding T3 b to themagnetic element T1 is 1:2. The output of the precharge circuit iselectrically connected to the first node SWAb and the second node SWBbso as to precharge the storage device Cbb. As the terminal voltage onthe storage devices Cba and Cbb are increased to Vin/2, the twoswitching power conversion units enter the soft switching state ofoutput voltage.

The terminal voltages of the storage devices Cba and Cbb of the twopower conversion circuits A1 and A2 are the same. Accordingly, inanother embodiment, only one precharge circuit is utilized to prechargethe storage devices Cba and Cbb of the two switching power conversionunits. As shown in FIG. 13B, the winding T3 of the precharge circuit ispositively coupled to the magnetic element T1 of the power circuit 22,and the turns ratio of the winding T3 to the magnetic element T1 is 1:2.The voltage VC3 on the capacitor C3 precharges the storage device Cbathrough the diodes D71 and D72. The voltage VC3 on the capacitor C3precharges the storage device Cbb through the diodes D73 and D74. Whenthe terminal voltages on the storage devices Cba and Cbb are increasedto Vin/2, the two switching power conversion units enter the softswitching state of output voltage. This implementation of prechargecircuit is simple, and the structure of the transformer is simplified aswell. The precharge circuit for the storage devices of the two powerconversion circuits, which are connected in parallel and interleavedwith each other, can be realized by disposing only four diodes.

The bootstrap circuits for the two power conversion circuits A1 and A2,which are connected in parallel and interleaved with each other, areshown in FIG. 14. In this embodiment, two bootstrap circuits areutilized to supply power for the driving circuits of the two powerconversion circuits respectively. The bootstrap circuit is similar tothat shown in FIG. 8A or FIG. 8C, and the detailed description thereofis omitted herein. In the power conversion circuit A1 and thecorresponding bootstrap circuit, the node voltage Vcc1 a equals Vcc whenthe second switch M22 a is turned on, and the node voltage Vcc1 asupplies power for the corresponding driving circuit to drive and turnon the first switch M12 a when the second switch M22 a is turned off.After the first switch M12 a is turned on, the node SWAa is shorted tothe node SWCa, and the node voltage Vcc2 a equals the node voltage Vcc1a. After the first switch M12 a is turned off, the node voltage Vcc2 asupplies power for the corresponding driving circuit to drive and turnon the first switch M11 a. Accordingly, the work principle of the powerconversion circuit A2 and the corresponding bootstrap circuit can bederived and is omitted herein.

Taking the power conversion system including two second power conversioncircuits as an example (i.e., X equals 2), the two second powerconversion circuits are connected in parallel and interleaved with eachother. As shown in FIG. 15, in the first power conversion circuit B1,the two ends of the storage device Cb10 c have a first node SWEc and asecond node SWFc respectively, and the two ends of the storage deviceCb11 c have a first node SWGc and a second node SWHc respectively. Inthe second power conversion circuit B2, the two ends of the storagedevice Cb10 d have a first node SWEd and a second node SWFdrespectively, and the two ends of the storage device Cb11 d have a firstnode SWGd and a second node SWHd respectively.

With regard to the two power conversion circuits B1 and B2 connected inparallel and interleaved with each other of FIG. 15, the correspondingprecharge circuit is shown as FIG. 16. As shown in FIG. 16, the powercircuit is a flyback circuit, and there are two identical prechargecircuits. The winding T3 c is positively coupled to the magnetic elementT1, and the turns ratio of the winding T3 c to the magnetic element T1is 1:2. The output of the precharge circuit is electrically connected totwo sets of isolation diodes D71 c/D72 c and D73 c/D74 c. The outputs ofthe isolation diodes D71 c and D72 c are electrically connected to thefirst node SWEc and the second node SWFc respectively for prechargingthe storage device Cb10 c. The outputs of the isolation diodes D73 c andD74 c are electrically connected to the first node SWGc and the secondnode SWHc respectively for precharging the storage device Cb11 c. Theother winding T3 d is positively coupled to the magnetic element T1, andthe turns ratio of the winding T3 d to the magnetic element T1 is 1:2.The output of the precharge circuit is electrically connected to twosets of isolation diodes D71 d/D72 d and D73 d/D74 d. The outputs of theisolation diodes D71 d/D72 d are electrically connected to the firstnode SWEd and the second node SWFd respectively for precharging thestorage device Cb10 d. The outputs of the isolation diodes D73 d/D74 dare electrically connected to the first node SWGd and the second nodeSWHd respectively for precharging the storage device Cb11 d. As theterminal voltages on the storage devices Cb10 c, Cb11 c, Cb10 d and Cb11d are increased to Vin/2, the two switching power conversion units enterthe soft switching state.

With regard to the two power conversion circuits B1 and B2 of FIG. 15,which are connected in parallel and interleaved with each other, in anembodiment, the corresponding precharge circuit includes four prechargecircuits of FIG. 5C. Under this circumstance, four windings arepositively coupled to the magnetic element separately, and the turnsratio of the winding to the magnetic element is 1:2. The four outputs ofthe four precharge circuits precharge four storage devices respectively.In another embodiment, the precharge circuit is similar to that shown inFIG. 5D. Different from the precharge circuit of FIG. 5D, the prechargecircuit for the two power conversion circuits B1 and B2 includes foursets of isolation diodes. Moreover, the one winding of the prechargecircuit is positively coupled to the magnetic element, the turns ratioof the winding to the magnetic element is 1:2, and the output of thewinding is electrically connected to the four sets of isolation diodes.The four outputs of the four sets of isolation diodes precharge the fourstorage devices respectively. When the terminal voltage on the storagedevice is increased to Vin/2, the two power conversion circuits enterthe soft switching state of output voltage. On condition that theprecharge requirement for the storage device is satisfied, the number ofthe winding and the number of the set of isolation diodes can be variedfreely to form the precharge circuit.

When the power conversion system includes the X second power conversioncircuits B1 to BX, which are connected in parallel and interleaved witheach other, the corresponding bootstrap circuit is similar to that shownin FIG. 8C, and the detailed description thereof is omitted herein.

In an embodiment, for satisfying the requirements of large currentoutput, the corresponding precharge and bootstrap circuits can beimplemented according to the precharge circuit of FIG. 13A, FIG. 13B orFIG. 13C and the bootstrap circuit of FIG. 14. In addition, if thenumber of the power conversion circuit is more (or even the number isodd), the corresponding precharge and bootstrap circuits can be derivedfrom the above embodiments and are omitted herein. In an embodiment, thediodes of the precharge circuit, the clamping circuit and the bootstrapcircuit of FIG. 13A, FIG. 13B, FIG. 13C and FIG. 14 may be replaced bythe controllable switches.

From the above descriptions, the present disclosure provides a powerconversion system and a magnetic component thereof. The power conversioncircuit of the power conversion system is a multi-phase buck converterwith extended duty ratio. Compared with the conventional buck circuitunder the same input and output conditions, the power conversion circuitof the present disclosure can increase the duty ratio and reduce theamount of voltage jump while turning on or off switches. Therefore, theswitching loss is reduced, and the efficiency is improved. Further, theprecharge circuit is utilized to precharge the storage device in thepower conversion circuit, thus the power conversion circuit enters asoft switching state, thereby reducing the voltage stress on theswitches of the power conversion circuit. Accordingly, it is allowed toemploy the switch component with low withstanding voltage so that thecost is reduced. Also, the switch component with low withstandingvoltage has low conducting inner resistance, which can improve the powerconversion efficiency and reduce the loss. In addition, the clampingcircuit is disposed at the two ends of the switch in the powerconversion circuit so as to clamp the peak voltage on the switch andprotect the switch. Meanwhile, the peak energy is absorbed and fed backto the circuit. Consequently, the loss of the peak energy is reduced,and the efficiency of the power conversion circuit is improved.Moreover, through disposing the bootstrap circuit and the drivingcircuit, the bootstrap supply function and the control of switches arerealized, which enhances the applicability of the power conversioncircuit greatly and benefits the miniaturization of the power conversionsystem product. The structure of the bootstrap circuit is simple so thatthe cost is low. Furthermore, through the special structure of themagnetic core assembly of the power conversion system, the AC magneticflux flowing through the winding pillar is shared. Accordingly, thethickness of the substrate of the magnetic core assembly is reduced, andthe height of the power conversion system product is reduced, whichmakes the power conversion system product become thinner and increasesthe applicability. Further, in the power conversion system, the powerdensity is improved, and the vertical thermal resistance is reduced. Inaddition, for the high power applications, the present disclosureutilizes a plurality of power conversion circuits connected in paralleland interleaved with each other to enlarge the load capacity of thepower conversion system. Through the phase difference among the controlsignals, the power conversion circuits can be connected in parallel andinterleaved with each other. Consequently, the current ripple at theinput side of the power conversion system is reduced, and it is allowedto employ the filter component with small volume so that the size of thepower conversion system is reduced.

While the disclosure has been described in terms of what is presentlyconsidered to be the most practical and preferred embodiments, it is tobe understood that the disclosure needs not be limited to the disclosedembodiment.

What is claimed is:
 1. A magnetic component, comprising: a magnetic core assembly, comprising two substrates, four winding pillars and an auxiliary pillar unit, wherein the four winding pillars and the auxiliary pillar unit are disposed on at least one of the two substrates and are located between the two substrates, a connecting line of centers of the four winding pillars forms a quadrangle, the quadrangle has a first diagonal line and a second diagonal line, and the auxiliary pillar unit is located among the four winding pillars; two windings, wherein one of the two windings is wound around two of the four winding pillars which are located on the first diagonal line, magnetic fluxes on the two winding pillars on the first diagonal line have the same direction and amount, the other winding is wound around the other two winding pillars located on the second diagonal line, magnetic fluxes on the two winding pillars on the second diagonal line have the same direction and amount, the directions of the magnetic fluxes on the two neighboring winding pillars are opposite, and the magnetic flux flowing out of any of the four windings flows to the two neighboring winding pillars and the auxiliary pillar unit to form three closed magnetic flux loops; and an air gap disposed on the auxiliary pillar unit.
 2. The magnetic component according to claim 1, wherein the magnetic component forms two inductors.
 3. The magnetic component according to claim 1, wherein the four winding pillars and the auxiliary pillar unit are disposed on one of the two substrates, or the four winding pillars and the auxiliary pillar unit are disposed on the two substrates.
 4. The magnetic component according to claim 1, wherein the four winding pillars are a first winding pillar, a second winding pillar, a third winding pillar and a fourth winding pillar respectively, the first and third winding pillars are located on the first diagonal line, the second and fourth winding pillars are located on the second diagonal, the auxiliary pillar unit comprises a first auxiliary pillar and a second auxiliary pillar, the first auxiliary pillar is located between the first and fourth winding pillars, and the second auxiliary pillar is located between the second and third winding pillars.
 5. The magnetic component according to claim 1, wherein the auxiliary pillar unit comprises an auxiliary pillar which is located at an intersection of the first and second diagonal line.
 6. A power conversion system, comprising: a power conversion circuit, comprising: an input port configured to receive an input voltage; an output port configured to output an output voltage; a first switching power conversion unit and a second switching power conversion unit connected in cascaded, wherein each of the first and second switching power conversion units comprises a first switch, a second switch and an inductor, in each of the first and second switching power conversion units, one terminal of the first switch is electrically connected to one terminal of the second switch and one terminal of the inductor, the other terminal of the second switch is grounded, the other terminal of the inductor is electrically connected to the output port, wherein the other terminal of the first switch of the first switching power conversion unit is electrically connected to the input port, and the other terminal of the first switch of the second switching power conversion unit is electrically connected to the first switch of the first switching power conversion unit; and a storage device electrically connected between the first switch and the inductor of the first switching power conversion unit; and a magnetic component, comprising: a magnetic core assembly, comprising two substrates, four winding pillars and an auxiliary pillar unit, wherein the four winding pillars and the auxiliary pillar unit are disposed on at least one of the two substrates and are located between the two substrates, a connecting line of centers of the four winding pillars from a quadrangle, the quadrangle has a first diagonal line and a second diagonal line, and the auxiliary pillar unit is located among the four winding pillars; two windings, wherein one of the two windings is wound around two of the four winding pillars which are located on the first diagonal line, magnetic fluxes on the two winding pillars on the first diagonal line have the same direction and amount, the other winding is wound around the other two winding pillars located on the second diagonal line, magnetic fluxes on the two winding pillars on the second diagonal line have the same direction and amount, the directions of the magnetic fluxes on the two neighboring winding pillars are opposite, and the magnetic flux flowing out of any of the four windings flows to the two neighboring winding pillars and the auxiliary pillar unit to form three closed magnetic flux loops; and an air gap disposed on the auxiliary pillar unit, wherein two windings of the two inductors of the first and second switching power conversion units are the two windings of the magnetic component wound around the magnetic core assembly.
 7. The power conversion system according to claim 6, wherein in each of the first and second switching power conversion units, the first and second switches operate periodically according to a switching period, the switching period has a duty ratio, and the duty ratio is larger than or equal to 30% and is smaller than or equal to 70%.
 8. The power conversion system according to claim 7, wherein a control signal of the first switch of the first switching power conversion unit is 180 degrees out of phase with respect to a control signal of the first switch of the second switching power conversion unit.
 9. The power conversion system according to claim 7, wherein in each of the first and second switching power conversion units, a control signal of the first switch is complementary to a control signal of the second switch.
 10. The power conversion system according to claim 6, wherein currents flowing through the two windings of the magnetic component make the magnetic flux flowing out of the winding pillar flow to the two neighboring and the auxiliary pillar unit to form the three closed magnetic flux loops.
 11. A power conversion system, comprising: a power conversion circuit, comprising: an input port configured to receive an input voltage; an output port configured to output an output voltage; a first switching power conversion unit and a second switching power conversion unit connected in cascaded, wherein each of the first and second switching power conversion units comprises a first switch, a second switch, a third switch and an inductor, in each of the first and second switching power conversion units, a first terminal of the first switch is electrically connected to the input port, a second terminal of the first switch is electrically connected to one terminal of the second switch, the third switch and one terminal of the inductor, the other terminal of the second switch is electrically connected to the second terminal of the first switch of the other switching power conversion unit, and the other terminal of the inductor is electrically connected to the output port; and two storage devices, wherein one of the two storage devices is electrically connected between the first switch and the inductor of the first switching power conversion unit, and the other storage device is electrically connected between the first switch and the inductor of the second switching power conversion unit; and a magnetic component, comprising: a magnetic core assembly, comprising two substrates, four winding pillars and an auxiliary pillar unit, wherein the four winding pillars and the auxiliary pillar unit are disposed on at least one of the two substrates and are located between the two substrates, a connecting line of centers of the four winding pillars from a quadrangle, the quadrangle has a first diagonal line and a second diagonal line, and the auxiliary pillar unit is located among the four winding pillars; two windings, wherein one of the two windings is wound around two of the four winding pillars which are located on the first diagonal line, magnetic fluxes on the two winding pillars on the first diagonal line have the same direction and amount, the other winding is wound around the other two winding pillars located on the second diagonal line, magnetic fluxes on the two winding pillars on the second diagonal line have the same direction and amount, the directions of the magnetic fluxes on the two neighboring winding pillars are opposite, and the magnetic flux flowing out of any of the four windings flows to the two neighboring winding pillars and the auxiliary pillar unit to form three closed magnetic flux loops; and an air gap disposed on the auxiliary pillar unit, wherein two windings of the two inductors of the first and second switching power conversion units are the two windings of the magnetic component wound around the magnetic core assembly.
 12. The power conversion system according to claim 11, wherein in each of the first and second switching power conversion units, the first, second and third switches operate periodically according to a switching period, the switching period has a duty ratio, and the duty ratio is larger than or equal to 30% and is smaller than or equal to 70%.
 13. The power conversion system according to claim 12, wherein a control signal of the first switch of the first switching power conversion unit is 180 degrees out of phase with respect to a control signal of the first switch of the second switching power conversion unit.
 14. The power conversion system according to claim 12, wherein in each of the first and second switching power conversion units, a control signal of the first switch is the same with a control signal of the second switch, and the control signal of the first switch is complementary to a control signal of the third switch.
 15. The power conversion system according to claim 11, wherein currents flowing through the two windings of the magnetic component make the magnetic flux flowing out of the winding pillar flow to the two neighboring and the auxiliary pillar unit to form the three closed magnetic flux loops. 